High frequency test balun

[0002] This application is a continuation-in-part of application Ser. No. 09/192,724, filed Nov. 16, 1998, issued Aug. 8, 2000 as U.S. Pat. No. 6,100,772. Said application/patent are hereby incorporated by reference.

[0003] The present invention relates to transmission systems for video and data signals. More specifically the invention relates to a low noise adapter device which is suitable for coupling testing equipment to a balanced two wire unshielded twisted pair for testing same.

[0004] Cable television (CATV) is transmitted over 75 ohm coaxial cable. Channels 2-60 are transmitted on the cable at frequencies ranging from 5 to 500 MHz. Many homes and commercial buildings have previously installed telephone cables consisting of unshielded twisted pairs. The standard unshielded twisted pairs (UTP) of telephone cables have a characteristic impedance of 100 ohms. It is often convenient to utilize this cable for transmission of video signals. Perhaps more significantly, UTP cable may also be utilized for transmission of computer data signals. Currently such cable and applications, such as local area networks, transmit computer data in the 20 to 30 MHz range. In the foreseeable future such transmission speeds on such cable may exceed 100 MHz.

[0005] There are difficulties associated with using the unshielded twisted pair cable for the above, particularly the transmission of CATV signals. Any attempt to utilize the UTP cable with unbalanced CATV signals or other unbalanced signals will result in unacceptable radiation and attenuation of the signals. Techniques such as shown in U.S. Pat. Nos. 5,633,614 and 5,495,212 also assigned to the owner of the instant invention, provide generally acceptable matching of the CATV coaxial cable with the UTP cable.

[0006] It is often useful or necessary to measure the balance and other characteristics of UTP cable particularly with reference to the potential usage of such cable for carrying CATB or data signals. Appropriate test equipment for performing such measurements, including network analyzers and signal generators, generally have a characteristic impedance of 50 ohms. Thus, attempts to make any quality measurements of the cable or other associated equipment such as connectors is impossible without suitably matching the test equipment characteristic impedance with that the UTP cable. Heretofore baluns and adapters suitable for such coupling had a restricted frequency range, for example up to 100 MHz. An adapter device is needed which offers high performance low noise coupling up to and beyond 350 MHz.

[0007] A passive, highly efficient, low noise adapter device includes a balun and noise reduction circuitry uniquely configured to converting an unbalanced signal line on a 50 ohm signal line to a balanced signal on a 100 ohm transmission line or vice versa. The device facilitates the use of commercially available and accepted test equipment for accurate transmission measurements on balanced twisted pairs of cables and connectors. A typical utilization includes an adapter device connected between the 100 ohm twisted pair cable and suitable test equipment such as a network analyzer and/or a signal generator for determining losses in the telephone wire and connectors.

[0008] A feature and advantage of preferred embodiments of the invention is that a much higher band width is provided by the device compared to conventional adapters.

[0009] A feature and advantage of preferred embodiments is that the device provides excellent noise reduction characteristics over the entire band width of the device.

[0010] FIG. 1 is an electrical schematic diagram of the circuitry of an embodiment of the invention.

[0011] FIG. 2 is an end elevational view of a device embodying the invention.

[0012] FIG. 3 is a front elevational view of the device of FIG. 2.

[0013] FIG. 4 is a block diagram of an application of the invention.

[0014] FIG. 5 is a block diagram of another application of the invention.

[0015] FIG. 6 is an exploded view of a device embodying the invention.

[0016] FIG. 7 is a side elevational view of a circuit board including principal components of an embodiment of the invention.

[0017] FIG. 8 is a top plan view of a circuit board suitable for the embodiment of FIG. 7.

[0018] FIG. 9 is a bottom plan view of the circuit board of FIG. 8.

[0019] FIG. 10A is a perspective view of the balun (T1) showing the windings.

[0020] FIG. 10B is a schematic figure of the balun (T1).

[0021] FIG. 11A is a perspective view of the common mode choke (T2).

[0022] FIG. 11B is a schematic view of the common mode choke (T2).

[0023] FIG. 12A is a perspective view of the signal splitter (T3).

[0024] FIG. 12B is a schematic view of the signal splitter (T3).

[0025] FIG. 13 is a block diagram of an application showing use of two of the inventions for measuring insertion loss of the invention.

[0026] FIG. 13A is a typical frequency response using two of the devices when configured as depicted in FIG. 13.

[0027] FIG. 14 is a block diagram of an application showing use of the invention for measuring return loss of the invention where the input signal is provided by an unbalanced 50 ohm impedance source and the load is measured across a balanced 100 ohm nominal resistance.

[0028] FIG. 14A is a typical frequency response of the device when configured as depicted in FIG. 14.

[0029] FIG. 15 is a block diagram of an application showing use of the invention for measuring return loss of the invention where the input signal is provided by a balanced 100 ohm impedance source and the load is measured across a 50 ohm nominal resistance.

[0030] FIG. 15A is a typical frequency response of the device when configured as depicted in FIG. 15.

[0031] FIG. 16 is a block diagram of an application showing use of the invention for measuring return loss of the invention where the input signal is provided by an unbalanced 50 ohm impedance source and the load is measured across a network of three resistors, each of 50 ohms nominal resistance.

[0032] FIG. 16A is a typical frequency response of the device when configured as depicted in FIG. 16.

[0033] FIG. 17 is a schematic of a further embodiment in accordance with the invention.

[0034] FIG. 18 is a schematic of a further embodiment in accordance with the invention.

[0035] FIG. 19 is a schematic of a further embodiment in accordance with the invention.

[0036] FIG. 20 is a schematic of a further embodiment in accordance with the invention.

[0037] FIG. 21 is a schematic of a further embodiment in accordance with the invention.

[0038] The use of input and output as used herein as a matter of convention for differentiating the ports on the device and does indicate or require that the signals must be transmitted in a particular direction through the device. As illustrated in the figures and as discussed below signals are transmitted in either direction through the device.

[0039] Referring to FIGS. 1, 2, and 3, the adapter device, enumerated 20, is shown in schematic form and as a component part. The adapter device generally comprises a housing 22 through which extend a first unbalanced input port 24, a second unbalanced input port 26, and a balanced output port 28. The balanced output port has two signal connectors 32, 33 and also has a grounded connector 34. The balanced output port signal connectors 32, 33 directly receive stripped wire of the unshielded twisted pair. The unbalanced input ports have coaxial type connectors 38 which may be SMA connectors or other suitable coaxial connectors.

[0040] Positioned in the housing, is a circuit board 42 as indicated by the dotted line in FIG. 3 which generally holds the components as indicated in the schematic of FIG. 1. The input port is connected to a balun 44 by a signal conductor 50 which extends to a first end 56 of a first winding 58. A second end 62 of the first winding connects to or comprises a first balun output lead 64. A second balun winding 70 has a first end 72 connecting to the first balun output lead and a second end 74 connecting to the circuit ground.

[0041] A third winding 82 has a first end 84 connecting to circuit ground 78 and a second end 86 connecting to a second balun output lead 90. A capacitor 94 extends across the first balun output lead 64 and the second balun output lead 90 and provides some suppression of high frequency parasitics.

[0042] A longitudinal common mode choke 96 has a pair of input leads 97, 98 and a pair of output leads 101, 102. The longitudinal choke 96 has a first winding 104, a second winding 105, a third winding 106, and fourth winding 107. The output leads 101, 102, are connected to first and second conductors 110, 112 of output port 28. A signal splitter 116 extends across the first and second conductors of the output port and has a center tap 118 between a first winding 120 and a second winding 121.

[0043] The center tap 118 of the splitter is connected to a resistor 125 which connects to the signal conductor 127 of the second unbalanced input port. The resistor, which minimizes parasitics, is 12.4 ohms in the preferred embodiment and is suitably in the range of 2 to 50 ohms. Details of the construction of the balun, choke, and splitter are discussed in detail below.

[0044] Referring to FIG. 4 one suitable application of the adapter device is displayed. A specimen 130 of unshielded twisted pair cable is connected to the balanced output ports 28A, 28B of two adapter devices 20A, 20B. A signal generator 134 is connected to the first unbalanced input port 24 of the adapter device 20A and a network analyzer is connected to the first unbalanced input port 24 of the adapter device 20B. The output of the signal generator 136 and the input 138 of the network analyzer 137 both has a first characteristic impedance of substantially 50 ohms. Cable 139 connecting the signal generator to the adapter device and the cable 140 connecting the network analyzer to the adapter device 20B each are 50 ohm coaxial cable. The specimen 130 would be an unshielded twisted pair cable having a second characteristic impedance of 100 ohms. The balun matching the first characteristic impedance. Thus, a signal of a specific frequency or a signal swept over a broad range of frequencies is detected and analyzed by the network analyzer 131 and appropriate return losses, insertion losses, and other suitable measurements can be determined by a convention measurement techniques.

[0045] Referring to FIG. 5, an alternative configuration is shown in which an adapter device 20 has a signal generator 141 connected to the second unbalanced input and a network analyzer 142 connected to the first unbalanced input. An unshielded twisted pair of cable 146 is connected to the output port 28 and has a 100 ohm resistor 148 connected at the termination 150 of said cable. Said configuration offers an alternate means of determining specific loss characteristics of the unshielded twisted pair of cable 146.

[0046] Referring to FIGS. 10A and 10B, details of the construction of the balun T1 is disclosed. Further specifications and construction procedures are disclosed in Table 1 below. The core is suitably a high permeability core in the range of 7500 or greater.

[0047] Referring to FIGS. 11A and 11B the longitudinal choke 96 is disclosed and has a first section 156 and a second section 158. The first section has a pair of stacked, cores with one being a relatively low permeability in a preferred embodiment of about 35 and the second stacked core has a permeability of about 750. Generally the permeability should vary by a magnitude of 10 or more.

[0048] The larger core in the second section 158 has a permeability in a preferred embodiment of 5,000.

[0049] The first, second, and third winding configured to provide an input impedance of substantially 50 ohms and an output impedance of substantially 100 ohms.

[0050] Further details are shown in table 2 below.

[0051] Each strand of Teflon® wire having a conductor portion and an insulation portion. The conductor portions and insulation portions configured so that the pair of windings has a characteristic impedance substantially matching the second characteristic impedance.

[0052] Referring to FIGS. 12A and 12B details of the configuration of the splitter 96 are disclosed. The splitter consists of a pair of cores stacked one with a low permeability 35 and the other with a relatively high permeability of 5,000. Appropriately the low permeability core is less than or equal to 35. Appropriately the high permeability core is greater than 4,000. Alternatively, the two cores appropriate would have a different in magnitude of 20 or more. Further details of construction are disclosed in the table below.

[0053] Referring to FIG. 6 details of the assembly of the housing is shown. In the ideal embodiment the housing 22 will be formed of brass although other comparable metals or other conductive materials may be used. The housing contains and encloses the circuit board 42 onto which or in proximity with are located the coaxial connectors 38 and the unshielded twisted pair connectors 32, 33.

[0054] Referring to FIGS. 7, 8, and 9, the positioning of the various components on the circuit board is disclosed in detail. The first input port 24 is positioned adjacent the balun (T1) 44 which is positioned adjacent the longitudinal common mode choke (T2) 96. Next is the splitter (T3) adjacent to the resistor 125. FIG. 8 discloses the component side of the board and FIG. 9 discloses the solder side of the board. With regard to the component side, juncture 150 is for the T1 single color finish and a second single color wire start. Juncture 152 is for T1 second wire finish. Juncture 153 is for T2 Teflon wire start. Juncture 154 is for T1 third wire start. Juncture 155 is for T1 third wire finish/and T1 second wire start. Juncture 156 is for T2 Teflon wire start. Juncture 160 is for T2 Teflon wire finish. Juncture 161 is for T2 Teflon wire finish. Juncture 162 is for T3 Teflon wire start and another Teflon wire finish. Juncture 163 is for the T3 Teflon wire finish. Juncture 164 is for the T3 Teflon wire start. The element number 170 is a 0.5 picofarads 50 volt capacitor, for example a surface mount multiplayer ceramic chip 0603 size capacitor. Said capacitor may appropriately range between 0.1 and 5 picofarads. The output signal conductor 171 are disposed on the circuit board and positioned to maintain the second characteristic impedance.

[0055] FIGS. 13, 13A, 14, 14A, 15, 15A, 16, and 16A, depict block diagrams and typical frequency response charts for the analysis and testing of device 20 and are intended to show typical performance of said device 20. Detailed descriptions are as follows:

[0056] FIG. 13 depicts a test configuration utilizing two devices (20A and 20B) and for the purposes of measuring insertion loss. Signal generator 134 is electrically coupled to the output side of device 20A by means of first shielded coaxial cable 139. The input side of device 20A is electrically coupled to the input side of device 20B by means of a suitably short segment of balanced, twisted pair telephone wire 131. The output of device 20B is electrically coupled to network analyzer 131 by means of second shielded coaxial cable 139. The second unbalanced input ports on both devices 20A and 20B remain unused in this configuration. Typical frequency response noted using said configuration is depicted in FIG. 3A. It will be appreciated that between the frequencies of 1 MHz and 500 MHz, the total signal loss for this configuration, is 2.4 decibels (dB), or, for a single device 20, 1.2 dB.

[0057] FIG. 14 depicts a test configuration for the purposes of measuring return loss over a 100 ohm resistor 148 load when excited by a 50 ohm unbalanced signal source. Signal generator 134 is electrically coupled to the output side of device 20 by means of shielded coaxial cable 139. The input side of device 20.1 is electrically coupled to the parallel combination of resistor 148 and network analyzer 131 by means of a suitably short segment of balanced, twisted pair telephone wire 29. Typical frequency response noted using said configuration is depicted in FIG. 4A. It will be appreciated that between the frequencies of 3 MHz and 350 MHz, the return loss of device 20 is a minimum of 20 dB.

[0058] FIG. 15 depicts a test configuration for the purposes of measuring return loss over a 50 ohm resistor 148.1 load when excited by a 100 ohm balanced signal source. Signal generator 134 is electrically coupled to the input side of device 20 by means of a suitably short segment of balanced, twisted pair telephone wire 129. The output side of device 20 is electrically coupled to the parallel combination of resistor 148.1 and network analyzer 131 by means of suitably short segments of shielded coaxial cable 139. Typical frequency response noted using said configuration is depicted in FIG. 15A. It will be appreciated that between the frequencies of 3 MHz and 350 MHz, the return loss of device 20 is a minimum of 20 dB.

[0059] FIG. 16 depicts a test configuration for the purposes of measuring common mode return loss over a load consisting of a network of three 50 ohm resistors 33A, 33B, and 33C, when excited by a 50 ohm unbalanced signal source. Signal generator 134 is electrically coupled to the output side of device 20 by means of shielded coaxial cable 139. The input side of device 20 is electrically coupled as follows: First port 26 is electrically coupled to first end of resistor 33A. Port 24 is electrically coupled to first end of resistor 33B. The first end of resistor 33C. The second ends of resistors 33A, 33B, and 33C are electrically coupled together and furthermore, electrically coupled to network analyzer 131. The remaining connection of network analyzer 131 is electrically coupled to ground. All connections on the output side of device 20 are by means of suitably short segments of balanced, twisted pair telephone wire 29. Connector 21 on device 20 is unused in this configuration. Typical frequency response noted using said configuration is depicted in FIG. 6A. It will be appreciated that between the frequencies of 1 MHz and 350 MHz, the return loss of device 20 is a minimum of 20 dB.

[0060] Still within the scope of the invention component values may be adjusted to provide different operating ranges, for example, a lower range of operation, such as 100 MHz to 10 MHz, which is used in some applications.

[0061] Referring to FIG. 17, a further embodiment of the invention is illustrated. This embodiment is similar to the first embodiment and has a balun 210, a capacitor 215 across the balun output leads, a common mode choke 222, and a common mode shunt or splitter 230. The resistor in series with balanced port 236 has been eliminated. Capacitive coupling between the 100 ohm balanced output 248 may be increased by utilizing a thinner wire insulation with a higher dielectric constant. The materials and configuration are otherwise suitably what is disclosed in the first embodiment.

[0062] Referring to FIG. 18 this embodiment is designed to provide excellent operating characteristics up to 650 MHz. This embodiment has five principle components: an impedance matching transformer or balun 262, a common-mode choke 268, a common-mode shunt 274, and two capacitors 280, 282.

[0063] The transformer 262 is used to match the unbalanced 50 ohm source impedance (i.e. a network analyzer) to a balanced 100 ohm impedance (i.e. networking cables, connectors). One small toroidal core with a permeability of 10,000 is wound in a similar configuration as the first embodiment using a multi-stranded, twisted wire.

[0064] The common mode choke 268 blocks any unwanted common mode signals from the balanced side of the circuit. A combination of a core with low permeability powdered iron with a permeability of 35 and high permeability cores, such as ferrite at 1800 and 5000, are stacked together and wound with a twisted wire to keep a 100 ohm characteristic impedance at the balanced pair.

[0065] The splitter or common mode shunt 274 is used to direct any common mode signal from the balanced pair to the C1 port to allow measurement of balance on the 100 ohm pair. A combination of low permeability iron core with a permeability of 35 and a core of high permeability, 5,000, are stacked together and wound with twisted wire that creates a high capacitive coupling between the balanced pairs. This higher capacitive coupling created by the twisted wire enhances the high frequency performance of the device.

[0066] The first capacitor 280 is placed across the unbalanced input of the T1 impedance matching transformer 262. This is suitably a small capacitance (under 10 PF) which enhances the high frequency performance of the device. The second capacitor 282 is placed across the balanced output of the impedance matching transformer 262. this is also a small capacitance, suitably under 10 pF, which enhances the high frequency performance of the device.

[0067] Referring to FIG. 19, this embodiment is suitably used to match the 50 ohm impedance of a network analyzer to 130 ohm cables and connectors. This embodiment is similar to the functionality of the first embodiment with the exception of a different impedance match and the elimination of the first embodiment common mode shunt (T3) since balance testing capability is not needed. This embodiment comprises principally three components: an impedance matching transformer 310, a common mode choke 318, and a capacitor 324.

[0068] This transformer of balun 310 is used to match the unbalanced 50 ohm source impedance (network analyzer) to a balanced 130 ohm impedance (cables, connectors). One small toroidal core with a permeability of 10,000 is wound in the same configuration as the first embodiment using a multi-stranded, twisted wire.

[0069] This component is used to block any unwanted common mode signals from the balanced side of the circuit. A combination of low permeability (powdered iron 35 perm) and higher permeability cores (i.i. ferrite with permeabilities of 1800 and 5000) are stacked together and wound with twisted Teflon® wire to keep a 130 ohm characteristic impedance in the balanced pair.

[0070] The capacitor 324 is placed across the unbalanced input of the T1 impedance matching transformer 310. This is a small capacitance (under 10 pF) which enhances the high frequency performance of the balun.

[0071] The second capacitor 282 is placed across the balanced output of the T1 impedance matching transformer 262. This is also a small capacitance (under 10 pH) which enhances the high frequency performance of the balun.

[0072] Referring to FIG. 20 a further embodiment is designed for the same functionality as the first embodiment, but a lower frequency range of 100 kHz to 100 MHz. To accommodate the lower frequency range, larger and higher permeability (10,000) ferrite cores configured as toroids are appropriately utilized. This embodiment is comprised principally of an impedance matching transformer 360, a common mode choke 368, a common mode shunt 376, and a capacitor 382.

[0073] The transformer 360 is used to match the unbalanced 50 ohm source impedance (network analyzer) to a balanced 100 ohm impedance (networking cables, connectors). A toroid with a permeability of 10,000 is wound as in the same twisted wire as the first embodiment of 040-0055 but in a different winding configuration as shown.

[0074] The common mode choke 368 is used to block any unwanted common mode signal from the balanced side of the circuit. Two cores with permeabilities of 10,000 are suitably stacked together and wound similar to the first embodiment to keep characteristic impedance of 100 ohms between the balanced output.

[0075] The common mode shunt 376 is used to direct any common mode signal to the C1 port to allow measurement of balance between the 100 ohm pair 382. A core with a permeability of 10,000 is wound with wire as on the first embodiment. Tefzel® wire is suitably used to create capacitive coupling between the balanced pairs 382 to improve high frequency performance.

[0076] The capacitor 382 is placed directly across the 100 ohm side of T1 to improve the product's high frequency performance.

[0077] Referring to FIG. 21, this embodiment is used to match the 50 ohm impedance of a network analyzer to 100 ohm telecommunication circuits and devices. This embodiment suitably does not have a common mode shunt since balance testing capability is not needed. This embodiment is principally comprised of impedance matching transformer 408, common mode choke 414, and two capacitors 420, 424.

[0078] The transformer 408 is used to match the unbalanced 50 ohm source impedance (network analyzer) to a balanced 100 ohm impedance. Suitably larger and high permeability (10,000) toroidal cores are implemented to obtain low frequency response. This component is wound as an isolation transformer to keep any DC current from flowing into the input of the analyzer.

[0079] The common mode choke 414 is used to block any unwanted common mode signals from the balanced side of the circuit. A large, high permeability (10,000) toroidal core is wound with twisted wire to keep consistent capacitive coupling between the 100 ohm balanced pair.

[0080] The first capacitor 420 is placed across the unbalanced input of the impedance matching transformer 408. This suitably has a capacitance of less than 30 pF which enhances the high frequency performance of the balun.

[0081] The second capacitor 424 is placed across the balanced output of the T1 impedance matching transformer. This suitably has a capacitance of less than 15 pF which enhances the high frequency performance of the balun.

[0082] The present invention may be embodied in other specific forms without departing from the spirit or essential attributes thereof, and it is therefore desired that the present embodiment be considered in all respects as illustrative and not restrictive, reference being made to the appended claims rather than to the foregoing description to indicate the scope of the invention.