Ultrafast Time Hopping CDMA and TDMA RF and Optical Communications: Code-as-Carrier, Multichannel Operation, High Data Rate Operation and Data Rate on Demand

In my U.S. Pat. No. 5,610,907 issued Mar. 11, 1997, I disclose a wireless RF time hopping code-division-multiple-access (CDMA) and time-division-multiple-access (TDMA) spread spectrum communications systems, and specifically to ultrafast systems, which use individual ultrashort pulses (monocycle) or small number of cycles (packets) signals in the picosecond (10.sup.-12) through nanosecond (10.sup.-9) to microsecond (10.sup.-6) range. Before transmission and after reception, the system functions as a digital communications system. The carrier for such wireless communications systems is neither a frequency, amplitude, phase nor polarization carrier, but is due to the precise timing arrangements in a sequence of individual pulses provided by the digital coding schemes.

Whereas most wireless RF communications systems in the art use frequency-domain receiver designs based on the heterodyne, or super heterodyne principle, the receiver of the present invention is a time-domain homodyne receiver. Whereas prior art uses coding, e.g., in direct sequencing or frequency hopping, to achieve spreading and despreading of the signal with resultant processor gain, the present invention uses an ultrashort pulse or packet as an individual signal, as well as coding which determines the timing of such individual pulses within a sequence. Information is carried in a transmission by the pulse position modulation technique, i.e., by precise micro-deviation from the pulse sequence timing set by the channel code.

Due to the use of orthogonal coding schemes and the use of ultrafast pulse sequence techniques, it is possible to provide extremely high data rate wireless point-to-point communications, as well as wide area multimedia communications.

The invention in my above-identified patent significantly increases the data rate of wireless RF communications by using orthogonal coding schemes in ultrafast time hopping CDMA communications both in point-to-point and broadcast mode; it provides a communications system which can coexist without interfering with, or causing interference to conventional RF transmissions or other ultrafast time hopping CDMA or TDMA users; it also provides wireless communications system which can interface with digital, e.g., optical fiber, communications systems; and a communications system which is robust against environmental notched filtering of frequency components in the transmitted signal; and provides communications system which has substantial range at modest power, is small in size, weight and is not costly to manufacture.

Briefly, the above features are achieved in an RF ultrafast time hopping CDMA and TDMA wireless communications system, which uses individual pulses and packets in a sequence of such pulses or packets, those individual pulses/packets being so short in duration (e.g., in the picosecond and nanosecond range) that the individual pulse signal energy is spread over very many frequencies simultaneously or instantaneously (instead of sequentially) with respect to a slow sampling system. A time hopping sequential code is also used to position these pulses/packets precisely in sequence providing optimum use of time-frequency space and also providing noninterfering transmission channels due to the orthogonality of the coding schemes used. The ultrashort nature of the individual pulses/packets used also permits the time duration of a frame to be divided into very many microintervals of time in which the signal could occur. This division into very many microintervals in a frame permits the availability of many possible coding schemes as well as many noninterfering transmission channels. Thus the ultrashort nature of the individual pulses, together with orthogonal coding schemes, permits the highest multichannel or aggregate data rates of any wireless communications system.

In one embodiment of the invention in my above patent, a communications system uses: (i) orthogonal codes which can be slaved to a single acquisition system/matched filter and which captures and assigns each code to unique decoding modems; (ii) correlators/acquisition systems/matched filters which are able to detect the ultrafast signals and retain memory of such capture over superframes of the order of a millisecond; (iii) pulsed power sources, antennas, encoding modems, oscillator-clocks, intelligence/data encrypters; and (iv) EPROMs to provide coding information to both encoding and decoding modems.

The present invention addresses optical time hopping code-division-multiple-access (CDMA) and time-division-multiple access (TDMA) spread spectrum communications systems, and specifically ultrafast systems and high data rate systems, which use individual ultrashort signals in the femtosecond (10.sup.-15) range, but could apply to signals of other temporal lengths. Before transmission and after reception, the system functions as a digital communications system. As in my above-identified patent, the carrier for such wireless communications systems is neither a frequency, amplitude, phrase nor polarization carrier, but is due to the precise timing arrangements in a sequence of individual pulses or wave packets provided by the digital coding schemes, i.e., a macrocode.

The present invention addresses a system and method, as in my above-identified patent, in which information is transmitted by a pulse or packet position modulation technique, i.e., by precise micro-deviation from the pulse/packet sequence timing set by the channel code or microcode, e.g., by pulse/packet modulation.

Due to the use of orthogonal coding schemes and the use of ultrafast pulse sequence techniques, it is possible to provide extremely high data rate optical fiber broadcast as well as point-to-point communications.

Accordingly, it is an object of the present invention to significantly increase the data rate of optical fiber communications (Gagliardi & Karp, 1995; Spirit & O'Mahony, 1995) by using orthogonal coding schemes in ultrafast time hopping CDMA or TDMA communications both in network broadcast and point-to-point mode.

It is a further object of the invention to provide an optical fiber communications system which can interface with digital, e.g., RF or wired line, communications systems.

Briefly, the above and other objects of the present invention are achieved in an optical ultrafast time hopping CDMA and TDMA wireless communications system, which uses individual wave packets or pulses in a sequence of such wave packets or pulses. A time hopping sequential code is also used to position these wave packets or pulses precisely in sequence providing optimum use of time-frequency space and also providing noninterfering transmission channels due to the orthogonality of the coding schemes used. This time hopping sequential code is referred to as the "macrocode" and identifies each information subchannel within the total channel. The data is encoded on each pulse or wave packet in modulation schemes which can be either parallel or serial--the latter case, a pulse position modulation scheme. The data encoding scheme is referred to as a "microcode".

As in the original invention, the ultrashort nature of the individual pulses used also permits the time duration of a frame to be divided into very many microintervals of time in which the signal could occur. This division into very many microintervals in a frame permits the availability of many possible coding schemes as well as many noninterfering transmission channels. Thus, the ultrashort nature of the individual pulses or wave packets, together with orthogonal coding schemes, permits the highest multichannel or aggregate at rates of any optical communications system.

In one embodiment of the present invention, a communications system uses: (i) orthogonal codes which can be slaved to a single acquisition system/matched filter and which captures and assigns each code to unique decoding modems; (ii) correlators/acquisition systems/matched filters which are able to detect the ultrafast signals and retain memory of such capture over superframes of the order of a millisecond; (iii) pulse train sources, encoders, oscillator-clocks, intelligence/data encrypters; and (iv) devices, e.g., acousto-optic modulators and holograms, to provide coding information to both encode and decode. The methods (o)--(iii) are also used by the original invention. The methods (iv) are specific to the present invention.

The above and other objects, advantages and features of the invention will become more apparent when considered with the following specification and accompanying drawings wherein:

FIG. 1a is a block diagram of a transmitter incorporating the invention configuration for an ultrafast time hopping CDMA wireless communications system, and FIG. 1b is a block diagram of a receiver configuration thereof,

FIG. 2 illustrates frames and subframes in an ultrafast time hopping CDMA wireless communication system incorporated in the invention.

FIG. 3 is a diagrammatic exposition of the subframe, frame and superframe,

FIG. 4 is a diagrammatic exposition of one method for achieving correlation and subframe sampling,

FIGS. 5a, 5b and 5c illustrate two orthogonal codes (FIGS. 5a and 5b), and their auto- and cross-correlation (FIG. 5c),

FIG. 6 illustrates a hyperbolic congruence code, p=11, a=1, 10.times.10 matrix,

FIG. 7 illustrates a hyperbolic congruence code, p=11, a=1, 50.times.50 matrix,

FIG. 8 illustrates the autoambiguity function for the hyperbolic congruence codes, p=11, a=1 and p=11, a=3, 10.times.10 matrix,

FIG. 9 illustrates the crossambiguity function for the hyperbolic congruence codes, p=11, a=1 and p=11, a=3, 10.times.10 matrix,

FIG. 10a illustrates a time-frequency representation of an ultrashort pulse of 1 nanosec. and a synchronous (e.g., heterodyne) receiver for a narrow-band sinusoid, and FIG. 10b is a bird's-eye-view of FIG. 10a.

FIG. 11 is a cut through the three-dimensional of FIG. 10,

FIG. 12 illustrates an acquisition system according to the invention,

FIG. 13 illustrates a detail of the acquisition system and decode modems,

FIG. 14 illustrates an optical mode broadcast network incorporating the invention,

FIG. 15 illustrates an optical mode point-to-point system incorporating the invention,

FIG. 16 is a diagrammatic illustration of macrocode and macrocode embedding incorporated in the invention,

FIG. 17 is a diagrammatic illustration of data recovery incorporated in the invention, and

FIG. 18 illustrates the interfacing aspects of the present invention.

In general physical terms the present invention is a system and method illustrated in FIGS. 14-18. I shall first describe the system and method of my U.S. Pat. No. 5,610,907, and referring initially to FIGS. 1a and 1b:

There are many possible embodiments of an ultrafast time hopping CDMA and TDMA system. The following is an embodiment which permits multichannel (high data rate) use.

1. Oscillator Clock 10, 10'. This circuit can use, e.g., GaAs MMIC technology, or other semiconductor technology, to convert DC power to a 2 GHz signal. The output signal of the oscillator clock will have sufficient power to drive the data gate circuitry and transmitter amplifier (during transmission of a pulse or packet). The oscillator clock is a crucial subcomponent requiring an accuracy >20 picoseconds in 1 msec., or about 20 parts in 10.sup.9.

The signal can be generated by a voltage-controlled oscillator phase-locked to a frequency stable reference signal.

2. Pulse Emitter and Antenna Module TA. During the transmission of an on-going pulse a sample of the oscillator signal is amplified and transmitted out of the antenna. An RF switching circuit (in pulse generator PG) driven by the comparator COMP trigger permits the oscillator clock to drive the transmitter amplifier chain for the duration of the pulse. The transmitter amplifier chain delivers the resulting RF pulse or packet to the antenna at a power level required by the system.

The amplifier can be, e.g., a cascaded set of GaAs MMIC chips, or other semiconductor technology. The bandwidth and impedance matching of these amplifiers can be achieved by, e.g., a distributed network of parallel MESFETs, or by other semiconductor methods. The input and output parasitic capacitances of the devices is absorbed by series inductances which in effect form a lumped element 50 ohm transmission line.

The antennas per se for both transmit and receive used can either be, e.g., of the nonresonant kind or, e.g., nondispersive TEM horn designs. In many cases, printed circuit methods can be used to fabricate the antennas on the circuit boards, as well as other methods of fabrication.

3. Acquisition Module AM. The acquisition module can be based on designs, e.g., using associative string processor modular technology or other means. This module is described in detail below.

4. Modems/Encoders and Modems/Decoders (Data Gate Circuitry). The data gate circuitry is common to both the transmitter and receiver. It can consist of, e.g., very high precision GaAs digital circuitry, or other semiconductor circuitry. The subframe counter is a free running counter driven by the clock oscillator. The output of the counter is compared to the look-up code corresponding to the frame counter.

The digital gate circuitry can be achieved using, e.g., ECL compatible source coupled logic on GaAs, or other semiconductor technology. Gate length and width can be chosen to reduce the parasitic capacitances such that loaded gate speed of less than 50 picoseconds can be met.

The receiver data gate counters are reset when a transmission is received. A high speed data latch is triggered to capture the output of the pulse detector during the subframes triggered by the code. The output of the data latch contains the transmitted data including error correction which corresponds to the position of the pulse within the subframe.

The transmitter data gate subframe and frame counters are free running. Whenever the subframe counter and codes match the pulse/packet generator is triggered causing a high speed pulse/packet to be transmitted. The pulse/packet position in the subframe corresponds to the data and error correction codes of the least significant bits at the inputs to the Acquisition Module.

5. Code EPROMs (Code Look-up 14, 14'). The code generation function can be performed by EPROMs in code look-up 14, 14' in the transmitter and receiver. Once per frame, a pulse/packet is generated by the frame counter EPROM. The code specifies in which subframe the pulse/packet will occur. With the use of more than one code (data rate on demand) the EPROM will provide more than one code to the transmitter and receiver. Alternatively, phase-shift registers can be used to generate the codes.

6. Pulse Detector (Rise Time Trigger 15). Background interference can be rejected by a rise-time triggering circuit, which is not merely a high pass filter. In order to achieve rise-time triggering, the RF signal can be passed through an envelope detector which is then fed through a high-pass filter before reaching the trigger threshold circuit. The high pass filter then differentiates the envelope and passes transients while rejecting slow changes.

7. Receiver (FIG. 1b). The receiver is a homodyne receiver (not a heterodyne receiver). The receiver preamplifier (not shown) needs a maximum of 40 db gain, no AGC, and a noise figure of approximately 5 db. The preamplifier of the receiver antenna RA feeds a pulse/packet detector 15 which output and ECL pulse for each detected pulse/packet. The pulse/packet detector 15 feeds the Acquisition Module AM, which includes correlator CO' which output triggers to the frame counter FC' and subframe counter SC'. The remainder of the receiver is similar or complementary to the transmitter. In a preferred embodiment, a high-speed counter SC' gates a data latch DL when the counter value matches the current main code value. The high-speed counter SC' wraps around at each frame interval. This wrap increments a frame counter FC', which is used to look up the code commencement in the EPROM 14'. The frame counter FC' wraps around at each superframe interval. The data latch DL' feeds the FEC decoder FEC' and optional decryptor DEC, which operates at the frame rate (about 1 Megabit per second). The receiver design is further described below.

With the use of multiple codes (data rate on demand) the EPROM 14', or phase-shift register, or other means of code generation, will provide more than one code to both the receiver and transmitter.

The Codes:

The wireless communications network can be used in either network or duplex arrangements. Two levels of coding are used in systems of the present invention. the major code is used to time the pulse transmission and allow multiple channels. Additionally, a forward error correction (FEC) code can be applied to the informational data before transmission. There is a large choice of error correcting codes (see Cipra, 1994).

The use of orthogonal codes permits the coexistence of multiple channels slaved together in the same superframe of a matched filter. Representative such codes are Quadratic Congruence (QC) codes, Hyperbolic Codes (HC) codes and optical codes (Titlebaum & Sibul, 1981; Titlebaum et al, 1991; Kostic et al, 1991). The discussion of coding requirements will be based on these codes.

The method for generating the placement operators for the QC code family provides a sequence of functions defined over the finite field, J.sub.p, where:

and p is any odd prime number. The functions are defined as:

where a is any element of J.sub.p except O and b,c are any member of J.sub.p. The parameter a is called the family index.

The difference function for the HC codes is the ratio of two quadratic congruences. The denominator polynomial of the ratio cannot have any zeros and the numerator is quadratic and has at most two zeros. Therefore, the HC codes have at most two hits for any subframe or frame shift. A sequence, u.sub.m (i),i=0,1,2, . . . , n-1, which is a member of a time hopping code can be constructed according to a method shown in FIG. 2. For example, pulses received in the first interval of the macro-window signify "1" and those received in the second interval signify "0". The number of bits in the subframe (microwindow) is determined by the precision of the data gate circuitry. Alternatively, the subframe can be used to encode analog information.

FIG. 5 shows the auto- and cross-correlation of two orthogonal codes. The autocorrelation is excellent indicating excellent transmission/reception capabilities. The crosscorrelation is extremely flat, indicating excellent cross-channel interference rejection.

FIG. 6 and FIG. 7 shows two HC codes, p=11, a=1, 10.times.10 matrix, FIG. 6, and, p=11, a=1, 50.times.50 matrix, FIG. 7 and FIG. 8 shows the autoambiguity function, for the HCC code, p=11, a=1, 10.times.10 matrix and FIG. 9 shows the cross-ambiguity function, for the HC codes, -=11, a=1 and p=11, a=3, 10.times.10 matrix.

The QC codes are defined as: ##EQU1## with 1.ltoreq.a.ltoreq.p-1 and 0.ltoreq.x.ltoreq.p-1 for p.times.p matrices.

The HC codes are defined as: ##EQU2## where ##EQU3## is the multiplicative inverse in the field J.sub.p and with 1.ltoreq.a.ltoreq.p and 1.ltoreq.x.ltoreq.p for p-1.times.p-1 matrices.

The QC and HC codes, due to Titlebaum and associates (Albicki et al, 1992; Bellegarda & Titlebaum, 1988-1991; Drumheller & Titlebaum, 1991; Kostic et al, 1991; Maric & Titlebaum, 1992; Titlebaum, 1981; Titlebaum 7 Sibul, 1981; Titlebaum et al, 1991), are representative orthogonal codes which can be used in the present invention, the ultrafast time hopping CDMA and TDMA communication systems. Other choices are available in the literature.

The major codes used in systems of the present invention are equally applicable to optical orthogonal coding procedures for fiber optical communications. The use of orthogonal codes permits the coexistence of multiple channels slaved together in the same superframe of a matched filter. For ease of explanation, the following terms are defined in Table 1.

An example of the relations between subframe, frame, superframe and channel is given in Table 2 for a code of length 1020, Table 3 for a code of length 508, and Table 4 for a code of length 250.

The subframe, frame and superframe relations are shown in FIG. 3.

The Receiver:

In conventional frequency domain heterodyne receivers the mixer is by far the preferred front-end component. In general, mixers are used to convert a low-power signal from one frequency to another by combining it with a higher-power local oscillator (LO) signal in a nonlinear device. Usually, the difference frequency between the RF and LO signals is the desired output frequency at the intermediate frequency (IF) at subsequent IF amplification. Mixing with local oscillators downconverts to intermediate frequencies and in the IF section narrowband filtering is most easily and conveniently accomplished. Subsequent amplification and detection is based on the intermediate frequency signal.

The operation of a detector in the mixing code results in a much lower conversion loss and is the reason for the excellent sensitivity of the superheterodyne receiver. The mixing action is due to a nonlinear transfer function:

where I and V are the receiver current and voltage If V.sub.RF sin .omega..sub.RF t is the RF signal and V.sub.LO sin .omega..sub.LO t is the LO signal, then the mixing products are:

The primary mixing products come from the second-order term. However, many other mixing products--may be present within the IF passband. Mixing produces not only a new signal but also its image, i.e., .omega..sub.LO .+-..omega..sub.RF. However, in the case of ultrafast time domain signals filtering could severely limit the amplitude of the signal and hence its range.

For example, the second-order term for a narrow-band frequency domain signal is:

but for a broad-band time domain ultrafast signal it is:

The output is then: ##EQU4## which possesses too many intermodulation products for use as an IF input.

Therefore, due to the broadband nature of the ultrafast individual signal, the synchronous (super) heterodyne receiver should not be the choice in receivers of the present invention due to the number of mixing products produced unless frequency selectivity for packets is desired. The receiver of choice for the present invention is a homodyne receiver.

A problem in definition arises in the case of the homodyne receiver. We take our definitions from optical physics (Born & Wolf, 1970; Cummins & Pike, 1974), not from radar engineering. Essentially, the heterodyne method requires a local oscillator to be mixed with the received signal and is a "self-beat" or autocorrelation method. The homodyne method is inherently a coherent method [cf. Born & Wolf, 1970, page 256]. The heterodyne method can be used with autocorrelation methods, e.g., after the mixing operation. The heterodyne method can even use a "coherent" local oscillator, but only with a narrowband signal. The distinguishing features between the two methods are that the homodyne method is a coherent (correlative) signal acquisition method with (a) no restrictions on the bandwidth of the received signal and (b) restrictions on the absolute timing of the signal bandwidth components. Conversely, the heterodyne method is a signal acquisition method with (a) no restrictions on the timing of the received signal and (b) restrictions on the bandwidth of the signal frequency components.

The various definitions of the heterodyne and homodyne methods are not consistent. For example, the IEEE Standard Dictionary of Electronic Terms (Jay, 1988) defines "homodyne reception" as "zero-beat reception or a system of reception by the aid of a locally generated voltage of carrier frequency"; and the McGraw-Hill Dictionary of Science and Technology (Parker, 1989) defines "homodyne reception" as "a system of radio reception of suppressed-carrier systems of radio telephony, in which the receiver generates a voltage having the original carrier frequency and combines it with the incoming signal. Also known as zero-beat reception."

Essentially, these definitions (Jay, 1988; Parker, 1989) refer to the generalized use of homodyning in a receiver with more than one mixing stage. "synchronous" detection is achieved by a method called "homodyning", which involves mixing with a signal of the same frequency as that being detected either by external or internal (i.e., with a phase loop) methods. Thus, recently the term "homodyne" has come to mean a method for the detection of narrowband signals and for restoring a suppressed carrier signal to a modulated signal.

Clearly the waters have been muddied concerning the definitions of the heterodyne and homodyne methods. However, the original optical physics definitions are specific in equating heterodyning as a method of signal acquisition using a local oscillator, and homodyning as a method of signal acquisition using a coherent method such as autocorrelation. Ultrafast, ultrashort pulse/packet signal acquisition requires the homodyne method because it is a coherent method and preserves timing information. It would not be right to coin new terms, because the present terms continue to survive relatively unambiguously in optical physics from whence they came. Therefore, we shall use the terms in the optical physics sense of those terms, but cautiously recognizing the danger of triggering the wrong associations.

The distinction between homodyne and heterodyne reception is significant and bears on the claims that the present invention is noninterfering to conventional, i.e., heterodyne, receivers. In FIGS. 10a and 10b, is shown both ultrafast, ultrashort pulse homodyne reception and narrow-band synchronous signal heterodyne reception in time-frequency space. FIG. 10a is a time-frequency representation of an ultrashort pulse of 1 nanosec. and a synchronous (e.g., heterodyne) receiver for a narrow-band sinusoid. Looking only from the frequency axis, the (exaggerated) spike of the ultrashort pulse would appear to overlap with the rising ridge of the narrow-band heterodyne receiver, i.e., the heterodyne receiver would appear to receive any of the ultrafast, ultrashort signals. However, looking at the total time-frequency plane representation, it can be seen that the ridge representation of the narrow-band synchronous heterodyne receiver does not extend down to the representation of the ultrafast signal representation. The synchronous, heterodyne receiver takes some time to respond and requires a number of cycles of a signal to receive that signal.

The distinction between the homodyne reception of the present invention and conventional heterodyne reception is shown in FIG. 11, which is a cut through FIG. 10a and viewed from the time side. The ultrafast, ultrashort pulse signal is shown to be diminished in amplitude for conventional heterodyne receivers of all attack (rise) times, even if the ultrashort signal's average frequency is at the center frequency of the heterodyne receivers. On the other hand, homodyne reception preserves signal amplitude and timing. While homodyne reception is preferred, heterodyne reception can be used.

The Acquisition System:

The acquisition system/matched filter of the present invention recognizes multiple codes (channels) over a superframe time period (1 msec. for a 1020 length code). FIG. 12 shows an Acquisition System, H, receiving F wireless signals from four channels S.sub.1 -S.sub.4 in asynchronous wraparound and triggers the receiving system decoding modems, S.sub.1 -S.sub.4.

FIG. 13 shows an embodiment in which the superframe of each transmission, S.sub.1 -S.sub.n, e.g., with codes of length 1020, is preceded by a preamble frame, e.g., of length 10. This preamble must be received in double wraparound for the case in which the channels, S.sub.1 -S.sub.n, are unsynchronized in their transmissions. In this embodiment, the preamble is the same code for all channels, even if unsynchronized, and acts as a synchronization alert to the Acquisition System, which performs recognition of the channel code and assigns a decoding modem. Unlike in the embodiment of FIG. 12, in the embodiment of FIG. 13 the Acquisition System is not functioning in wraparound mode, but is alerted to the beginning of a transmission of a superframe by the preamble, which is in double wraparound.

The Networks:

The network applications of the present invention are diverse and range from high data rate duplex systems, to building-to-building systems, to the linking of optical fiber networks between such buildings, to within building communications, to LANs and WANs, to cellular telephones, to the "last mile" of Global Grid communications, and to "smart highway" applications (Varaiya, 1993) (e.g., intelligent windshields, etc), etc.

Application Areas:

Wireless WANs and LANs;

Personal Communications Networks;

Cellular Telephones;

Building Automation/Security Systems;

Voice communications;

Bridge & Router Networking;

Instrument Monitoring;

Factory Automation;

Remote Sensing of Bar Codes;

Vehicle Location;

Pollution Monitoring;

Extended-Range Cordless Phones;

Video TeleConferencing;

Traffic Signal Controls;

Medical Monitoring and Record Retrieval Applications;

Remote Sensing;

Factory Data Collection;

Vending Machine Monitoring;

"Last Mile" Global Grid Communications.

The invention includes the following features:

a) Apparatus and methods of ultrafast, ultrashort pulse/packet transmission.

b) Apparatus and methods of transmitting sequences of such ultrafast, ultrashort pulses/packets.

c) Apparatus and methods of pulse/packet interval modulating such sequences according to a macro-coded scheme.

d) Methods of pulse/packet interval modulating such sequences within a microwindow of the macrowindow set by the code such that information can be encrypted in that microwindow.

e) Codes stored in matrix form as, e.g., associative memories and with superframes of received signals matched against the stored codes.

f) Codes which are orthogonal codes and the temporal coding of the sequence of ultrafast, ultrashort pulses/packets constitutes the carrier for the transmission.

g) A homodyne, not a synchronous heterodyne, receiver.

h) An acquisition system/matched filter/correlators which synchronizes to a superframe transmission and assigns such transmissions to an appropriate decoding modem on the basis of code recognition.

i) Multichannel operation which provides high overall or aggregate data rate (e.g., .sup..about. 500 mbs for maximum multichannel operation).

The attached paper entitled "Comparison of Communications . . . and disclosure statement" and the paper entitled "Reference" filed herewith are incorporated herein by reference.

Summarizing, an ultrashort pulse/packet time hopping code-division-multiple-access (CDMA) and time-division-multiple access (TDMA) RF communications system in the time frequency domain comprises a transmitter including:

a) a short duration pulse/packet generator for generating a short duration pulse/packet in the picosecond through nano-second to micro-second range and a controller for controlling the generator,

b) code means connected to the controller for varying the time position of each short pulse/packet in frames of pulses/packets in orthogonal superframes of ultrafast time hopping code division or time division multiple access format,

c) precise oscillator-clock for controlling such timing,

d) encoding modems for transforming intelligence into pulse/packet position modulation form,

e) antenna/amplifier system connected to said means for generating for receiving and broadcasting said short duration pulse/packets as a coded broadcast signal,

receiver means, said receiver means including:

a) antenna/amplifier system for receiving the broadcast signal,

b) homodyne receiver for receiving and decoding the coded broadcast signal, and

c) one or more utilization devices connected to the homodyne receiver. The coding means generates sequences of ultrafast, ultrashort pulses/packets, and an interval modulator for interval modulating the sequences according to a macrowindow encoded format. The macrowindow encoded format set by the assigned code includes microwindows and the pulse/packet interval modulator modulates the position of an individual pulse/packet within a microwindow of each macrowindow set by the code such that information can be encrypted in each of the microwindow. The code means includes codes stored in matrix form as, e.g., associative memories and with superframes of received signal representing the full assigned code, orthogonal to other assigned codes, matched against the stored codes. Preferably, the codes are orthogonal codes with the temporal coding of the sequence of ultrafast, ultrawideband pulses constituting the carrier for transmission by the antenna system.

The homodyne receiver includes a bank of decoder/modems, an acquisition system/matched filter for synchronizing to a superframe transmission, identifying coded sequencers in the superframe and assigning the transmissions to a selected decoder/modem on the basis of code recognition. The system is adapted for multichannel operation and provides a high overall data rate in the 500 mbs range for maximum multichannel (aggregate channel) operation.

The present invention is illustrated in general physical terms in FIGS. 14-17:

FIG. 14 illustrates a broadcast network mode in which data sources (A)--either RF, IR, optical or electrical line--are given an optical orthogonal macrocode, and the data, encoded in microcodes (wave packets) within the macrocode packet sequence, is transmitted asynchronously along optical fibers to a hub system (C) which identifies each orthogonal macrocode/channel and assigns a decoder (B) to each macrocode or sequence of wave packets. The data is then recovered at the decoders in RF, optical or electrical form. The broadcast network mode can also have an embodiment in which no hub system is required and the data sources (A) interact with the data recovery points (B) without intermediary systems. In this embodiment, the data stream is continuously sampled by the data recovery units and wave packets are identified for subsequent decoding by their occupancy in a macrocode "wave packet" stream or train.

FIG. 15 illustrates a point-to-point mode, in which data sources (A)--either RF, optical or electrical line--are given optical orthogonal macrocodes which are slaved together, and the data, encoded in microcodes (wave packets) within the macrocode, is transmitted synchronously along optical fibers to data recovery decoders (B) for each macrocode/channel or sequence or train of packets. The data is then recovered at the decoders in RF, IR, optical or electrical form.

FIG. 16 illustrates the data encoding in the microcode embedded in the user's/channel's macrocode. The macrocode defines the user (if only one code is allocated to a user) or a one channel within a multichannel system. The macrocode is an orthogonal optical code and is identified by a first matched filter. The microcode can be an error correcting code and is identified by a second matched filter behind the first.

FIG. 17 illustrates the data recovery in both the broadcast and point-to-point modes: A. the macrocode or wave packet sequence identification either by the hub system or by the individual data recovery unit. In this embodiment, the hub system and the individual data recovery units are represented by acousto-optical modulators (AOM). Each black dot in the code matrices (see original patent) represents a wave packet carrying the microcode. The individual data recovery units only address the wave packets arriving at the time appropriate to the individually assigned orthogonal macrocodes. B. The data is encoded at the microcode level. A representative 1011 "word" or wavepacket is shown corresponding to a position in the macrocode indicated by a black dot. The microcode word can be processed or decoded either in sequential form or in parallel.

FIG. 18. The optical methods addressed in the present invention can be interfaced with the methods addressed in the original patent. In this figure, the data can arrive at the transmit switch in optical, IR, electrical wire or RF form and be decoded at the receive switch in optical electrical wire and RF form, with the intervening link in RF form as addressed in my U.S. Pat. No. 5,610,907.

In general physical terms the present invention is a system described in FIGS. 14-17. The various component parts are described in the System section and the specifics of the coding schemes are described in the Codes section. As in my U.S. Pat. No. 5,610,907, the code is the carrier.

The System:

There are many possible embodiments of an ultrafast optical time hopping CDMA and TDMA system, all of which use laser light sources and an optical fiber network (cf. Gagliardi & Karp, 1995; Spirit & O'Mahony, 1995). The following is an embodiment of the invention which permits multichannel or aggregate (high data rate) use.

1. An optical wave packet stream can be encoded in a macrocode form or optical orthogonal code form by a variety of methods, e.g., by acousto-optical modulators, or holograms or clock devices, both real or emulated (c.f. Weiner et al, 1992; Ford et al, 1994; Hillegas, 1994; Sun et al, 1995).

2. The data can be encoded into the individual wave packets in a microcode form by a variety of methods, e.g., holographically, k or by clocking or by acousto-optical or other optical methods such as spatial light modulation. (FIG. 16 illustrates one embodiment).

3. The macrocodes can be received at a hub system for identification and assignment to individual data recovery units, or directly to the individual data recovery unit, which then sample and identify the unique macrocode for the specific unit. This function can be performed in a number of ways, e.g., by acousto-optical modulators, holograms or clock devices, both real or emulated. (FIG. 14 illustrates one embodiment.)

4. The macrocodes can be slaved together for ultrahigh data rate transmission in point-to-point operation. (FIG. 15 illustrates one embodiment.)

5. The data can be decoded from the individual wave packet microcode into either a sequential bit stream or in parallel form by a variety of methods, e.g., holographically, or by clocking or by acousto-optical or other optical methods such as spatial light modulation. (FIG. 17 illustrates one embodiment.)

6. The system can be used in an all-optical network, an all-RF network, an IR-RF network, an all IR network, optical-RF network, a wire-optical network or a wire-RF network, etc. (FIG. 18 illustrates one embodiment.)

The Codes:

The optical orthogonal codes which define the macrocode are similar to the RF orthogonal codes of the original invention except that whereas an RF signal can have two polarities, +1 and -1, as well as the value of zero, 0, an optical orthogonal code can only take on the two values of +1 and 0, or -1 and 0. Therefore, the statistical representation of optical orthogonal codes are related to, but differ in some respects, from RF orthogonal codes (cf. Nguyen et al, 1992; Chung & Kumar, 1990; Chung et al, 1989).

Application areas include:

Extremely high data rate all-optical fiber communication links;

Extremely high data rate optical fiber communication links interfacing with RF and electrical wire communication links.

The present invention includes:

(a) methods of extremely high data rate optical fiber transmission.

(b) methods of transmitting sequences of such ultrashort wavepacket sequences or trains in a macrocode.

(c) methods of encoding data within each wavepacket of a wavepacket sequence or train as a microcode.

(d) codes which are optical orthogonal codes and the temporal coding of the sequence or train of ultrashort pulses or wavepackets constitutes the carrier for the transmission channel;

(e) macrocode recognition schemes and microcode data recover units.

(f) multichannel operation which provides high overall data rate (e.g., .sub..about. 500 gigabits/sec-.sub..about. terabits/sec for maximum multichannel or aggregate operation).

In addition to the references cited in my U.S. Pat. No. 5,610,907, the following additional references are noted:

Chung, H. & Kumar, P. V., Optical orthogonal codes--new bounds and an optimal construction. IEEE Trans. Information Theory, 36, 866-873, 1990.

Chung, R. K., Salehi, J. A. & Wei, V. K., Optical orthogonal codes: design, analysis, and application. IEEE Trans. Information Theory, 35, 595-604, 1989.

Ford, J. E., Fainman, Y., & Lee, S. H., Reconfigurable array interconnection by photorefractive correlation, Applied Optics, 33, 5363-5377, 1994.

Gagliardi, R. M. & Karp, S., Optical Communications, 2nd Edition, Wiley, N.Y., 1995.

Hillegas, C. W., Tull, J. X., Goswami, D., Strickland, D. & Warren, W. S., Femtosecond laser pulse shaping by use of microsecond radio-frequency pulses. Optics Letters, 19, 737-739, 1994.

Nguyen, Q. A., Gyorfi, L., Massey, J. L., Constructions of binary constant-weight cyclic codes and cyclically permutable codes. IEEE Trans. Information Theory, 38, 940-949, 1992.

Spirit, D. M. & O'Mahony, M. J., High Capacity Optical Transmission Explained, Wiley, N.Y., 1995.

Sun, P. C., Mazurenko, Y. T., Chang, W. S. C., Yu, P. K. L. & Fainman, Y., All-optical parallel-to-serial conversion by holographic spatial-to-temporal frequency encoding, Optics Letters, 20, 1728-1730, 1995.

Weiner, A. M., Leaird, D. E., Reitze, D. H. & Paek, E. G., Femtosecond spectral holography. IEEE J. Quantum Electronics, 28, 2251-2261, 1992.

While preferred embodiments of the invention have been illustrated and described, it will be appreciated that other embodiments, adaptations and modifications of the invention will be readily apparent to those skilled in the art and embraced by the claims appended hereto.