Method and Apparatus for Non-Destructively Determining Ingredients of a Sample

The present invention is directed generally to nondestructive analysis of materials and more particularly to an analysis method and apparatus which utilizes electromagnetic radiation to measure one or more constituents of a sample of material, for example, the fat content of a sample of meat.

While the non-destructive test method and apparatus of the invention is useful for determining constituent content of various constituents of many materials, the disclosure will be facilitated by addressing the problem of determining the fat to lean ratio in a meat product.

Many meats and meat products are generally evaluated nutritionally on the basis of the ratio of lean meat to fat in the product. Additionally, the prices at which such products are sold are often based at least in part on this ratio. Hence, an accurate determination of the percentage fat or alternatively, the percentage lean in a given meat product assume some economic importance for both the processor and the retailer.

Heretofore, the only reliable method of accurately determining fat or lean content of a sample has been by destructive testing. That is, a sample of the product must be fully cooked and the rendered fat product assayed to determine its percentage as a constituent of the product. Quite apparently, this destructive method of testing is not suitable for relatively frequent tests of relatively large numbers of samples of meat products. The prior art has developed an alternative, electromagnetic test method and apparatus for non-destructively performing such a measurement. One such apparatus is shown for example in U.S. Pat. No. 3,735,247 to Harker. While the method and apparatus disclosed therein has proven useful in many applications, there remains room for yet further improvement.

For example, some problems have arisen with respect to proper sample preparation to ensure both accuracy and repeatability of the measurements obtained by prior art devices. In this regard, it is important to accurately weigh each sample and accurately position the weighed sample in the prior art measurement apparatus.

Additionally, the fundamental measurement technique involved in the prior art apparatus involves inserting a sample into an electromagnetic coil which is shielded against extraneous influence. However, the shield must be open at least at one end thereof to allow entrance and egress of a sample. Such shielding has proven difficult to achieve. Moreover, for accurate operation, the measurement coil must extend well beyond the ends of the sample and the shield must extend well beyond the ends of the coil. While the latter requirement is easy to achieve, it is sometimes difficult to assure that an operator will properly position a sample within the coil.

The foregoing prior art electromagnetic test apparatus and method is based upon the differing electrical properties of lean and fat animal tissue. In this regard, primarily of interest is the relatively large ratio of conductivity between fat and lean tissues which may vary between 5 and 100. However, a ratio of between 1.1 and 10 has also been found between typical lean and fat dielectric constants. Heretofore, it has been proven difficult to separate the electrical effects upon the measurement coil of the conductivity of a sample on the one hand and the dielectric constant on the other hand. Since the relative magnitudes of these two electrical properties may vary considerably in a given sample, it is important to adequately isolate but one of these properties for measurement purposes. Since the conductivity ratio of fat to lean is typically considerably higher than the dielectric constant ratio, it is preferably to isolate the former for measurement purposes. In the prior art apparatus it has proven difficult to eliminate the effects of dielectric constant and assure measurement of substantially only the conductivity of a sample.

The prior art method and apparatus is also based primarily upon power losses and phase shifts in the sample which are reflected back to the field source in the measurement coil. It will be recognized that the power loss is related to conductivity while the phase shift is related to dielectric constant. In order to accurately measure conductivity, then, relatively small incremental power losses must be accurately measured. To ensure accuracy of the power loss measurement, the prior art apparatus required a considerable power input to the measurement coil and hence relatively bulky and expensive high-power electrical and electronic components.

When utilizing a coil as the primary measurement apparatus, additional problems are encountered with the known variations in magnetic and electric field components produced by a coil over the radius or along the axis of a sample of material placed in the coil. For example, it is known that the transverse magnetic (TM) component of the electromagnetic field is advantageous in that the electric field remains constant with changing radius. However, in the prior art apparatus it has been found that at the frequencies required for measurement (100 kHz to 10 MHz), and with the dimensions of a coil necessary to accommodate an adequate sample, it is difficult or impossible to generate a uniform TM mode. Hence, the above-mentioned prior art apparats utilizes primarily the transverse electric (TE) mode for obtaining measurements. Unfortunately, the TE mode field lines run parallel to the axis of the coil and hence the field varies considerably over the radius of a sample within the coil. Since the fat or lean content can also be fairly assumed to vary within a given sample either axially or radially, the foregoing factors present some difficulty in obtaining accurate and repeatable measurements.

Accordingly, it is a general object of the present invention to provide a method and apparatus for non-destructively determining the fat content of a sample of a meat product which substantially avoids the problems of the prior art.

A more specific object is to provide a method and apparatus for measuring fat content in meat products by providing an electromagnetic field and measuring the conductivity of a sample of a meat product introduced into the electromagnetic field.

A related object is to provide a test apparatus in accordance with the foregoing objects which provides a substantially continuous and uniform electromagnetic field throughout a volume into which a sample is introduced.

Another object is to provide a test apparatus in accordance with the foregoing objects which is responsive substantially only to the real power loss within the electromagnetic field.

Yet another object is to provide a test apparatus in accordance with the foregoing objects wherein the electromagnetic field contains substantially no net axial electric field components.

A related object is to provide a test apparatus in accordance with the foregoing objects which is relatively simple and inexpensive and yet highly reliable in operation.

In accordance with one aspect of the invention, a test apparatus is provided for measuring the proportion of at least one constituent in a sample of material, which constituent bears a known relationship to the electrical conductivity of the sample. The test apparatus comprises a sensor including receptacle means for receiving a sample of material therein and field producing means for producing an electromagnetic field within said receptacle, for substantially confining said electromagnetic field to a predetermined, fixed volume within said receptacle means, and for producing a substantially constant magnitude electromagnetic field throughout said predetermined, fixed volume.

In accordance with another aspect of the invention, the foregoing test apparatus is further provided with monitoring circuit means coupled with said sensor and responsive thereto for producing an output signal which bears a predetermined relationship with the real impedance of said sensor both when empty and when the sample is received therein, said output signal thereby bearing a predetermined relationship with the conductivity of said sample, when present, said monitoring circuit means being further substantially unresponsive to the dielectric constant of either or both of said sensor or said sample.

The foregoing as well as other objects, features and advantages of the invention will be more readily understood upon reading the following detailed description of the illustrated embodiment together with reference to the drawings, wherein:

FIG. 1 is a side elevation, partially broken away and partially in section of a test apparatus in accordance with the invention;

FIG. 2 is a perspective view, partially broken away, of components of the test apparatus of FIG. 1;

FIG. 3 is a side elevation of a field producing component of the test apparatus of FIG. 1;

FIG. 4 is an end view of the field producing component of FIG. 3;

FIG. 5 is a side elevation of a field control component of the apparatus of FIG. 1;

FIGS. 6A and 6B, taken together, form a schematic circuit diagram of one portion of a test circuit useful with the test apparatus of FIG. 1;

FIGS. 7A and 7B, taken together, form a schematic circuit diagram of a further portion of a test circuit useful with the test appartus of FIG. 1;

FIG. 8 is a schematic circuit diagram of another portion of a test circuit useful with the test apparatus of FIG. 1;

FIG. 9 is a schematic circuit diagram of the circuits of a reference element useful in verifying accurate operation of the test apparatus of the invention;

FIG. 10 is a schematic circuit diagram of an auxiliary unit useful in making field modifications in the operation of the apparatus of the invention; and

FIG. 11 is a schematic circuit diagram of a power supply circuit for the foregoing circuits.

Referring to the drawings, and initially to FIG. 1, a preferred form of a test apparatus in accordance with the invention is designated generally by the reference numeral 10. This test apparatus 10 includes a case or housing 12 which conveniently houses all of the components thereof. In this regard, a suitable display of panel 14 may be conveniently mounted on a front side of the casing or housing 12.

In accordance with the principles of the invention, an electromagnetic field is produced in a fixed and preferably cylindrical volume within the housing 12. In the illustrated embodiment, a field producing component or coil 16 is mounted within the housing 12 for this purpose. In the illustrated embodiment, this field producing component or coil 16 is mounted to a cylinder 18, preferably of a transparent non-conductive plastics material, having an open outer end 19 for the ingress and egress of a sample of material to be placed within the electromagnetic field produced thereby for testing purposes. In this regard, a separate, transparent sample container 20 is also preferably of a non-conductive plastics material and a right circular cylinder and preferably is removable with respect to the coil 16. In FIG. 1, the sample container or cylinder 20 is shown fully inserted with respect to the coil 16, whereby it assumes a position substantially concentrically or coaxially aligned within the coil 16. Preferably, a suitable removable cap 21 is also provided for the sample cylinder 20.

In the illustrated embodiment, a sample receiving chamber or receptacle is defined concentrically or coaxially within the coil 16 by a further, fixed transparent and non-conductive plastics material cylinder or tube 22 which slidably receives the sample cylinder 20. In this regard, an end wall 24 is defined within the receptacle 20 and thereby defining a fully inserted or test position thereof within the test apparatus 10. Preferably this end wall 24 is provided with a drain tube or channel 25 to facilitate cleaning of the interior of the fixed cylinder or tube 22.

In order to further control the field produced by the coil 16, as will be more fully described later, a further cylindrical member 30 is concentrically or coaxially mounted therewith. In the illustrated embodiment, this further cylinder 30 is coaxially mounted intermdiate the coil 16 and receptacle 22.

In accordance with a preferred feature of the invention, the sample cylinder 20 also mounts a temperature probe 32 which protrudes upwardly from an enclosure 34 therefor which is placed just above the bottom wall 26. Within this enclosure 34 a plurality of electrical and electronic circuit components, designated generally by the reference numeral 36, are mounted. Briefly, these circuit components 36 accomplish temperature measurment of the sample received in the cylinder 20 in response to the temperature probe 32 and deliver an output signal by way of mating components 37.

Preferably, the enclosure 34 and the walls 24 and 26 are of a transparent and electrically non-conductive material, whereby both light impulses and electromechanical impulses may readily pass therethrough. As will be described more fully later herein, the temperature measurement probe 32 and related circuitry 36 may therefore be isolated within the sample cylinder 20, having no direct mechanical contact between the mating electrical components 37 and cooperating mating compontents, designated generally by the reference numeral 38, within the test apparatus 10. Consequently, the temperature measurement apparatus including the probe 32 and circuitry 34 is carried completely within the sample cylinder 20 for intimate contact with the sample contained therein. However, suitable electrical power for the circuit 34 as well as a signal path for the temperature signals developed thereby are passed to monitoring circuitry carried within the housing 10 by way of the respective mating components 38 and 37.

Additionally, a sensory arrangement comprising a light emitting diode (LED) 39 and a light responsive transistor 41 are mounted on the tube 16 at opposite sides of the tube 22. This sensor arrangement serves to verify proper fitting of the tube 20 with a sample of material, as will be more fully described later.

With respect to the foregoing description, reference is also invited to FIG. 2, wherein the concentric mounting of the cylinders 18, 22 and 30 and the slidable insertion therein of the cylinder 20 is illustrated.

As best viewed in FIG. 3, the field producing component or coil 16 comprises an elongate, right cylindrical tube, preferably of a transparent, non-conductive plastics material which carries a plurality of generally circular windings designated generally by the reference numeral 40. In accordance with a feature of the invention, these windings 40 are respectively located and electrically interconnected so as to produce a substantially uniform and continuous electromagnetic field over a predetermined volume within the coil 16. In this regard, the electromagnetic field strength along the axial length of the coil 16 is approximated by the diagram 50 therebelow.

In order to maintain this field 50, a pair of relatively broad end windings or shorting coils 42 and 44 are provided and, as will be seen later, are electrically connected with ground potential to provide well-defined zero field points at either end of the field 50. Intermediate these two end windings 42 and 44 a plurality of intermediate windings or field coils 46 are arranged to produce the substantially uniform and continuous field 50. In the illustrated embodiment these windings 46 each comprise a thin trip of electrically conductive material, preferably copper, wound substantially concentrically about the cylinder 18. These copper strips 46 are substantially evenly spaced along the axial-length of the coil 16 intermediate the end windings 42 and 44, which are preferably considerably broader copper strips also concentrically wound about the cylinder 18. Advantageously, sample measurement is therefore confined to a fixed measurement volume collectively defined by the windings 46 and the field 50 produced thereby.

In the illustrated embodiment, the field windings 46 are twelve in number and are arranged in four groups of three along the axial length of the cylinder 18.

Advantageously, these groups of three windings 46 are arranged to direct current flow in alternating clockwise and counterclockwise directions, respectively, about the cylinder 16, these clockwise and counterclockwise directions being indicated in the end view of FIG. 4, to which reference is also invited. In this regard, a first three windings 46-1, 46-2 and 46-3 direct current flow in the clockwise direction, and the winding 46-3 is coupled in series with the next succeeding winding 46-4 so as to reverse the current flow to the counter-clockwise direction. Hence, the succeeding three windings 46-4, 46-5 and 46-6 direct current in a counterclockwise direction, whereupon the windings 46-6 passes current to the next winding 46-7 to be directed in the clockwise direction to and through winding 46-9. Similarly, current flow is again reversed through the remaining three windings 46-10, 46-11 and 46-12. Accordingly, a substantially zero net current flow is accomplished along the axial length of the coil 16.

The axially outermost ends of the respective first and last windings 46-1 and 46-12 are both coupled to circuit ground. Similarly, a midpoint of the windings 46 comprising the axially innermost ends of windings 46-6 and 46-7 is also coupled to circuit ground. In this regard, a suitable grounding strap 52 is provided to tie together these three grounded points of the windings 46.

In accordance with a further feature of the invention, suitable alternating current is fed to the coil 16 at points intermediate the above-described grounded points of the windings 46. In this regard, respective adjacent ends of the windings 46-4 and 46-5 receive an alternating electrical signal and similarly, adjacent ends of windings 46-9 and 46-10 receive the same alternating electrical signal through a common signal strap 54. Hence, it will be seen that net current flow throughout the windings 46 is substantially zero. The foregoing electrical interconnections are also indicated in circuit schematic form in FIG. 7, as will be seen hereinbelow.

In order to render the coil 16 responsive substantially only to the conductivity or real impedance component of the measurement volume defined by the field windings 46, and hence of the portion of a sample of material introduced into this measurement volume, the net axial electric field is also held at a substantially zero value. In addtion to the coil configuration described above, the field control cylinder 22 aids in achieving this reduction of axial electrical field components. In this regard, the cylinder 22 is also preferably of a transparent, non-conductive plastics material and carried a plurality of axially extending field shorting strips radially spaced about its circumference, as indicated generally by the reference numeral 56. In the illustrated embodiment, these shorting strips 56 comprise elongate strips of electrically conductive material such as copper foil, similar to the material utilized to form the field windings 46 of coil 16 as described above. In the illustrated embodiment, these axial strips 56 are sixteen in number and are evenly spaced about the circumference of the cylinder 22. Moreover, the axial length and axial location of each of these strips 56 is such that when the cylinder 22 is coaxially mounted within the coil cylinder 16, each of the axial strips 56 extends at least from one end coil 42 to the other end coil 44, and hence throughout the entire magnetic field produced in the volume surrounded by the field windings 46. In order to ensure shorting out of substantially all electric axial field components these strips 56 preferably extend somewhat into the volume enclosed by the respective end shorting windings 42 and 44.

The foregoing components advantageously produce a well-defined electromagnetic field containing substantially no axial electric field components. Hence, the signal lead or strap 54 will experience a net power consumption which varies substantially only in response to the real power loss or conductivity of the volume defined within the field windings 46. Advantageously, the conductivity of meat products is known to vary considerably with the fat content thereof. Hence, measurement of real power absorption which is directly proportional to electrical conductivity, that is, the real part of impedance, provides a good measure of the fat content of a sample of a meat product. In this regard, a sample of a meat product may readily be placed within the controlled field volume by the simple expedient of providing a suitable filling marking or line about the exterior of the sample cylinder 21, as designated by reference numeral 60 in FIG. 2. Hence, since the bottom wall of the sample cylinder 20 extends somewhat into the area of the end shorting coil 44, and the top marker 60 extends somewhat into the volume within the opposite end shorting coil 42, filling of the sample cylinder 21 from the bottom wall 34 up to at least the marking 60 will assure the placement of a portion of the sample within and completely filling the field 50 in the volume defined by the field coils or windings 46. In this regard, it is preferable to uniformly pack the sample of product into the sample cylinder 21. Sample preparation of this type is most readily carried out with ground meat products. Advantageously, in view of the uniform field provided as described above, having substantially zero axial electric components, the weight of the sample introduced into the sample cylinder 21 has no effect upon the measurement of fat content thereof. Hence, the weight of a sample need not be carefully controlled as with many prior art measuring devices.

Reference is next invited to FIGS. 6A and 6B wherein a first portion of a novel monitoring circuit for use with the test instrument of FIG. 1 is illustrated in circuit schematic form.

Referring initially to FIG. 6A, in the illustrated embodiment the measurement and display circuitry is microcomputer-based. In this regard, a microcomputer 100 is provided, and is preferably of the type generally designated MK38P70/02 (MOSTEK).

This microcomputer 100 drives the display 14 by way of a suitable display driver integrated circuit 102. In the illustrated embodiment, the display 14 comprises a liquid crystal display panel including three sevensegment alphanumeric characters 104, 105 and 106 and a decimal point 107 for displaying three significant digits to the nearest tenth. Also included are a plurality of selectively energizable message characters 109 for indicating various test functions. The display driver 102 preferably comprises a component of the type generally designated HLCD438.

Additionally three switches 117 and three corresponding LED display elements 121 are provided in the illustrated embodiment for selecting and indicating selection of one of three different products or materials for testing. The microcomputer 100 responds to each switch 117 by selecting appropriate data from a memory 110, as will be shortly described, for the testing of a corresponding product or material.

The microcomputer 100 is programmed to operate upon data received from the measurement coil 16 by way of related circuitry illustrated in FIG. 7, and also to receive temperature data from the probe 32 and related circuits 34, 40 and 38.

A plurality of predetermined empirical constants for calculating percentage fat or lean content of a sample of one or more materials are provided in an electronic memory unit 110. In the illustrated embodiment this memory unit 110 comprises a non-volatile array random access memory (NOVRAM). Preferably this NOVRAM 110 comprises a 64.times.4-bit memory of the type generally designated XC2210(XICOR). The empirical data is arranged in 64, 4-bit words therein. Hence, 4-bit data transfer but (Cl, D2, D4, D8) is coupled to input ports 112 of the microcomputer 100 and 6-bit address bus A.sub.0 -A.sub.5 is coupled to output ports 114 of the microcomputer 100. A chip select line CS and other control inputs WE, AR and STO of the NOVRAM 110 are coupled to a suitable output porst 116 of the microcomputer 100. Briefly, in operation, calibration and other empirical data for use in testing a plurality of different products is stored in the NOVRAM 100, where it is accessible for modification in the field, if desired. This NOVRAM 110 normally operates to bidirectionally communicate this data from its RAM portion to the microcomputer 100. However the non-volatile (an E.sup.2 PROM) portion of the NOVRAM 110 is also automatically energized to hold the data from the RAM in non-volatile form when power is switched off or otherwise lost to the NOVRAM 110. Upon "power up" the data is then automatically shifted back to the RAM portion. The microcomputer 100 is programmed to accomplish this data shifting by way of its connections to control terminals CS, WE, AR and STO of the NOVRAM 110. Additionally, a field test unit (FTU) to be described later with reference to FIG. 10 may be utilized to verify or change the data in the NOVRAM 110. When this FTU is coupled in circuit with the microcomputer 100, it completes the circuit therefrom to the STO input of the NOVRAM. Data may then be shifted to the RAM portion for verification and/or modification, and then shifted back to the PROM portion in similar fashion by the microcomputer 100 upon command from the FTU of FIG. 10. Hence, suitable empirical data for testing any desired product may be placed in the NOVRAM 110.

Input data from one of the temperature probe 32 or the field measurement coil 16 is selected by the microcomputer in response to operator selection by a "temp/data" control switch 119 which feeds an input 120 of the microcomputer 100. In response thereto, the microcomputer issues a control signal on a port 121 thereof. This control signal from the port 121 drives a logic network 122 which receives the temperature data at a first input 124 and the measurement coil data at a second input 126. The output of this logic network 122 feeds an external interrupt (EXT. INT.) port of the microcomputer 100. Hence, the data entering the external interrupt port corresponds to either temperature data or coil measurement data as selected by the switch 119.

Additional control ports of the microprocessor function to select a reference element for calibration purposes (REFR) and to effect automatic zeroing calibration (NULL). Additionally, a control port 128 of the microcomputer 100 may be left open circuited or tied to ground by manipulation of a switch 130. When the port 128 is left in open circuit condition, the microcomputer 100 functions to calculate and display the percentage fat content of the sample. Conversely, when the switch 130 is closed, grounding the port 128, the microcomputer 100 responds by "inverting.infin. the readout to display the lean content of the sample. The remaining ports of the microcomputer 100 interface with the above-mentioned field test unit (FTU) to be described later with reference to FIG. 10.

In accordance with a preferred form of the invention and referring also to FIG. 6B, the temperature measurement circuitry 36 which is carried within the removable enclosure 34 is coupled with the microcomputer 100 by a novel, non-contact arrangement. In this regard, suitable electrical power for energizing the circuitry 36 is provided by an inductive link-up including a coil 132 which is in alignment with a complementary secondary coil 134 forming a part of the circuit 36. The first coil 132 is driven by an oscillating signal provided by a divider circuit 138 and selectively gated by the control terminal 120 at a gate 142. This divider circuit 138 is described later herein.

When a temperature measurement is to be taken, the signal at the port 120 also causes the temperature data from the line 124 to be fed to the EXT. INT. port of the processor, by way of the logic switching circuit 122. A suitable drive transistor 140 (e.g. Vn88AF) is provided for driving the coil 132 with the signals provided at the gate 142. Further in this regard a conventional buffer component 144 and a suitable current limiting resistor 146 are provided in series between the gate 142 and the base electrode of the transistor 140.

The temperature circuit 36 is electrically coupled with a temperature sensing element 150 carried in the temperature probe 32. In the illustrated embodiment, this temperature sensing element 150 comprises a temperature responsive adjustable current source of the type generally designated LM334Z. This temperature responsive element 150 is tied to the input of a voltage-to-frequency converter 152 which in the illustrated embodiment comprises an integrated circuit V-F converter of the type generally designated LM331AN. The output of this voltage-to-frequency converter provides a temperature-dependent variable frequency drive to an LED 154 coupled to a suitable output terminal thereof and provided with a suitable current limiting resistor 156. Suitable passive RC components are coupled with other electrodes of the voltage-to-frequency converter 152 in conventional fashion to result in excitation of the LED 154 at a frequency correlative with the temperature sensed at the temperature sensor element 150.

Suitable DC power is provided to the voltage-to-frequency converter 152 from the secondary coil 134 by way of a conventional integrated circuit voltage regulator component 158, which in the illustrated embodiment comprises a voltage regulator of the type generally designated 7805. A suitable rectifying diode 160 zener reference 166, and smooting capacitors 162, 164 are provided at the input of the voltage regulator 158 from the secondary coil 134. The frequency-temperature analog represented by the periodic flashing of the LED 154 is sensed by a light responsive transistor 161 which forms a part of the circuit 38 mounted at the wall 24 of the cylinder 22 as described above with reference to FIG. 1. This light sensitive transistor 161 is wired as a switching transistor receiving a suitable positive voltage bias through a current limiting resistor 163 at its collector electrode while the emitter electrode thereof is tied to ground. The collector electrode thus comprises the signal output and feeds the temperature related frequency signal back to the input 124 of the logic signal selection circuit 122 by way of a suitable series coupled capacitor 165 buffer component 167.

In accordance with a preferred form of the invention, the microcomputer 100 also receives a signal at a port 129 thereof indicating whether the sample cylinder 20 is properly filled with a sample of material. In this regard, a suitable circuit to be described later with reference to FIG. 8 is utilized to monitor the condition (properly filled or not) of the cylinder 20 and to provide a corresponding signal at the port 129.

referring now to FIG. 7A, a circuit for measuring the real power loss and hence conductivity of a sample placed within the measurement volume defined by the measurement coil 46 is illustrated. The electromagnetic field producing coil 16 and in particular the respective windings 42, 44 and 46 thereof described above with reference to FIG. 3 are here illustrated in circuit schematic form. As mentioned in the above description thereof, the end windings 42 and 44 are tied to circuit ground, as are the axially outermost ends of the windings comprising the measurement coil 46 and the centermost point thereof. The signal points are tied to points in the coil 46 equidistant between the grounded end and the center point and are fed to one input 171 of an integrated circuit modulator component 170.

In the illustrated embodiment the integrated circuit modulator 170 comprises a balanced modulator of the type generally designated MC1496 (MOTOROLA). This same input is also fed a suitable alternating signal from a secondary winding 172 of a transformer 174 whose primary winding 176 receives a suitable high frequency energizing current from a conventional crystal oscillator circuit 178.

In the illustrated embodiment, the oscillator circuit 178 includes an 10 MHz crystal coupled to an oscillator integrated circuit of the type generally designated SL1680C wired with together with suitable capacitors (now shown) wired to produce a signal at a 10 MHz frequency. This 10 MHz signal is fed through a suitable buffer circuit including a transistor 180 wired as an emitter-follower and the amplitude of the resultant signal is adjusted by a suitable potentiometer 182. This 10 MHz signal is fed through a tuned filter circuit comprising a pair of fixed inductors 184, 186, a pair of fixed capacitors 188, 190 and an adjustable tuning capacitor 192 for tuning the filter circuit. The signal from the tuned filter circuit feeds the primary coil 176 mentioned above.

The foregoing circuit is driven by a 488 Hz signal which feeds the base electrode of a transistor 194. The collector electrode of this transistor 194 is coupled in circuit with the buffer circuit including the transistor 180 for "chopping" the signal from oscillator 178 at a 488 Hz rate in response to the 488 Hz signal at the base electrode of the transistor 194.

The foregoing 488 Hz signal is derived from the microprocessor 100 of FIG. 6A by the divider network 138 mentioned above. Briefly, the divider network 138 comprises a first divider component 195 and a second divider component 197 wired essentially in series circuit. The first divider component 195 is divide-by-four counter/divider of the type generally designated 74LS74, while the second divider component 197 is a 14-stage binary counter/divider of the type generally designated CD4020. In this regard the 15.625 KHz signal fed to the gate 142 of FIG. 6A is derived from the Q6 output of the divider 197 while the 488 Hz signal is taken from the Q11 output thereof. The divider network 138 receives a suitably buffered input from a 4 MHz crystal 193 which also provides the crystal input to the microcomputer 100 for deriving a suitable internal master oscillator frequency.

The modulator 170 also receives the signal from the transformer secondary 172, but from the end thereof opposite its connection to the signal points of the measurement coil 46. A 90.degree. fixed phase difference is introduced into this latter signal to the modulator 170 by the inclusion of a plurality of in-parallel fixed capacitors 196. The phase difference is further adjusted to substantially exactly 90.degree., to compensate for any circuit tolerances, by an adjustable capacitor 198 also wired in parallel with the fixed capacitors 196. Remaining terminals of the modulator integrated circuit component 170 are coupled with suitable DC voltage levels and passive components to produce a modulated output signal across outputs 171 and 173 which is proportionate to Zcos.theta. where Z is the real impedance at the sample coil and 46 and .theta. is the 90.degree. phase difference set in by the capacitors 196 and 198.

These outputs 171 and 173 are AC coupled to the respective inverting and non-inverting inputs of a differential AC amplifier comprising an operational amplifier 200 which is also provided with an offset reference voltage at its inverting input from a suitable resistor 202. The output of this operational amplifier 200 feeds the inverting input of a further operational amplifier 204 whose non-inverting input is tied to ground and whose output 206 feeds a suitably amplified signal nZcos.theta., to the like-numbered input 206 of the portion of the circuit shown in FIG. 7B. Referring now to FIG. 7B, input 206 feeds the normally open (NO) terminal of a dual analog switch component 208. In the illustrated embodiment, this analog switch 208 comprises one-half of an analog switch component of the type generally designated LF13333 (National Semi-Conductor). This analog switch 208 also has a normally closed (NC) portion which is fed directly from the output of the operational amplifier 200 of FIG. 7A. The normally closed and normally open portions of the analog switch 208 are driven synchronously by the 488 Hz signal from the divider chain 138 of FIG. 6A mentioned above. This is the same 488 Hz signal feeding the input of the transistor 194 to chop the input signal to the balanced modulator circuit of FIG. 7A. The outputs of the normally closed and normally open contacts of the analog switch 208 are fen in common through a suitable resistor 210 to the inverting input of an operational amplifier 212 which is provided with suitable feedback by way of a capacitor 209 and a resistor 211. The non-inverting input of the op amp 212 is tied to circuit ground. Suitable additional components are illustrated with the operational amplifier 212 whereby this circuit acts as a low pass filter.

Advantageously, the use of the same synchronized 488 Hz signal at the input of the circuit of FIG. 7A and again to drive the analog switch component 208 of FIG. 7B permits this circuit to operate in a synchronous modulated fashion. That is, the switch 208 is driven as a synchronous detector for the signals fed thereto from the circuit of FIG. 7A. Advantageously, the scheme of synchronous modulation and detection substantially eliminates the requirement for precise gain and offset error control and adjustment throughout the circuit of FIG. 7A and 7B. For example, the balanced modulator 170 of FIG. 7A exhibits a significant, though usually stable DC offset voltage. However, it is not possible to predict the DC offset from component to component. This problem is substantially solved, however, by modulating the signal with the 488 Hz "chopper" effect described above and thus coupling only the AC components of the outputs of the modulator 170 to the following circuits. Moreover, by AC coupling the signal and thus eliminating DC components, the output of the balanced modulator tends to closely track the inputs without regard for temperature or voltage supply drift effects, thus greatly improving the signal-to-noise ratio of the downstream signal. Additionally, the use of the lowpass filter circuit including the op-amp 212 permits the circuit to act essentially as a high Q filter substantially rejecting DC errors and noise. In this regard, the operational amplifier 212 and associated circuitry is set for a bandpass of substantially 1 Hz centered on the 488 Hz signal.

In this regard, operation of the synchronous detector comprising the analog switch 208 may be disabled selectively in accordance with the program of microprocessor 100 by way of the NULL output thereof. This NULL output feeds the base electrode of a suitable switching transistor 215 whose emitter electrode is grounded and whose collector electrode feeds the disable terminal of the analog switch component 208. Referring again to FIG. 7A, the reference control output REFR from the microcomputer 100 is coupled in circuit with a switching transistor 213 which selectively energizes a switching component 215 to switch the reference resistor 217 into parallel circuit with the coil 46 at its input 171 to the balanced modulator 170. In accordance with the operation of the invention, the microcomputer is programmed to switch this reference resistor into circuit during the measurement cycle both when the sample is absent from the receptacle 22 and again when the filled sample cylinder 20 has been introduced into the sample receptacle 22. This then allows the microcomputer 100 to operate by taking difference readings, that is by noting not only the difference between the "sample present" and "sample absent" signals developed by the circuit of FIG. 7B, but also to note the difference in readings obtained both with a sample present and a sample absent as the reference resistor is switched in and out of the circuit. Since the value of this reference resistor 217 is carefully selected and known and programmed into the microcomputer 100, the sample present and sample absent readings can further be advantageously more accurately determined by calculating them as a difference from the known value of the sample resistor as well as noting their absolute values with the sample resistor not in circuit.

The use of the synchronous modulation and dectection substantially eliminates any necessary gain adjustments in the circuits of FIGS. 7A and 7B. This is true because the chopped output signal essentially represents a chopped input signal, that is to say the measurement signal alternating in a substantially 50% duty cycle with a no signal input. Moreover, since the reference element 217 is switched into circuit both when the sample cell is empty and the sample cell is filled with material, a second difference value is introduced into the modulated signal, that is the difference in signal level with the reference resistor in circuit and out of circuit. Hence, the modulated or chopped output signal of the modulator represents a "difference of differences", that is the difference between no signal and measurement signal present in a substantially 50% duty cycle and the superimposed difference of the reference resistor in and out of circuit, respectively. Hence, the synchronous detector continuously gives a signal which is in effect analagous only to the difference in gains between these levels, whereby any drifts in the absolute values of the gains provided by the various components in the circuits of FIGS. 7A and 7B does not effect the accuracy of the measurement.

Referring again to FIG. 7B, the output of the lowpass filter at the output of the op amp 212 feeds on input of a voltage-to-frequency converter circuit (V-F)214. In the illustrated embodiment, this V-F converter 214 comprises a component of the type generally designated RC4153 (RAYTHEON). The V-F converter 214 is provided with suitable passive components as illustrated to achieve the desired voltage-to-frequency conversion ratio, as is known in the art. The resultant frequency signal is fed out at an output 216 to the like numbered input of the circuit of FIG. 6A. Referring briefly again to FIG. 6A, it wll be seen that this output 216 feeds a remaining input of the selection logic circuit 122 for selection thereof as an input to the microcomputer 100. As described previously, the output of the V-F converter comprises the "data" input selected by manipulation of the switch 119. Reference is next invited to FIG. 8 wherein a sensor circuit associated with the LED and phototransistor 39, 41 described above with reference to FIG. 1 is illustrated. It will be remembered that the LED 39 and photosensitive transistor 41 are positioned at opposite sides of the cylinder 16 to detect the presence of a sample in the sample cylidner 20 to a proper or suitable level to assure accurate measurement. This system acts as an automatic backup on the operator's proper filling of the sample tube with reference to the fill line 60 as also mentioned above.

The LED 39 and photosensitive transistor 41 are again shown in circuit schematic form in FIG. 8. The remainder of the circuit comprises a phase locked loop component (PLL) 400 which receives the output of the photosensitive transistor 41 by way of intervening amplification stages comprising operational amplifiers (op amp) 402 and 404. In the illustrated embodiment, the PLL 400 comprises an integrated circuit component of the type generally designated NE567 (SIGNETICS).

The photosensitive transistor 41 is wired as an emitter follower and feeds its output to the inverting input of the first op amp 402. The output of the op amp 402 is AC coupled to the inverting input of the op amp 404 which is provided with suitable feedback by way of a resistor 406 and a capacitor 408. The output of the second op amp 404 is then AC coupled to the input of the Pll 400. The collector electrode of the transistor 41 together with the non-inverting inputs of the op amps 402 and 404 are biased from a suitable source of DC potential. The output of the op amp 402 also feeds the base electrode of the transistor 41 by way of suitable resistors 410 and 412 and the junction of these two resistors 410, 412 is tied to ground by the series combination of a further resistor 414 and a capacitor 416. The oscillator output of the Pll 400 drives the LED 39 by way of a drive transistor 418 which in the illustrated embodiment comprises a darlington pair component of the type generally designated MPSA18.

From the foregoing it will be seen that the phase lock loop 400 thus locks into its own oscillator frequency which is utilized to drive the LED 39. That is, the photosensitive transistor 41 is energized in response to the frequency of the LED 39 and the output of this phototransistor forms the input to the PLL 400. Hence, the circuit of FIG. 8 forms a very sensitive and stable LED sensor circuit for detecting interruptions in the beam between the LED 39 and the phototransistor 41. In this regard the output of the phase lock loop 400 feeds a line 420 which forms the input to the port 129 of the microcomputer 100 of FIG. 6A.

Referring now to FIG. 9, a reference tube is also provided which is substantially identical in configuration to the sample tube 20 defined above. However, the circuit contents of this reference tube provide reference temperature and data (i.e., sample data) output signals by means of the circuit components contained therein and illustrated in FIG. 9 in circuit schematic form.

The reference temperature output is provided by means of an LED 300 which is coupled in series with a suitable current limiting resistor 302 and a diode 304 across a suitable secondary coil 306. This secondary coil is positioned in the sample tube so as to be in registry with the primary coil 132 described above with reference to FIG. 6B. Hence, this reference temperature circuit provides a predetermined output by way of the light responsive transistor 161 described above with reference to FIG. 6B, with which the LED 300 is positioned in alignment.

The sample data reference circuits comprises the parallel combintaion of a resistance 308 of known value and an inductance 310, which represent the resistance and inductance of a single turn of one-quarter inch copper foil to provide a referencce coil element. This reference element is carried on a reference tube so as to be inserted within the sample volume defined by the coil 16 described above. Hence, the reference tube may be inserted in the same fashion as the sample receiving cylinder or tube 20 to produce a reading to the microprocessor 100 by way of the circuit of FIG. 7A and 7B so as to verify the proper operation of the circuits of the invention.

Referring briefly to FIG. 10, the field test unit (FTU) comprises a separate unit which is here illustrated in circit schematic form. Briefly, this field test unit may be coupled with the microprocessor 100 of FIG. 6A by way of the like-designated terminals illustrated in FIG. 10 and in FIG. 6A.

Briefly, the field test unit is operative for selectively reviewing and reprogramming as desired the contents of the NOVRAM 110 of FIG. 6A. It will be remembered that these contents relate primarily to empriical data utilized by the microprocessor 100 in calculating the fat content of each of a plurality of different products or materials.

In this regard, the FTU of FIG. 10 includes a conventional four-by-four keboard 400 which is coupled in an X-Y matrix to a suitable decoder integrated circuit 402. In the illustrated embodiment this decoder circuit 402 comprises an integrated circuit component of the type designated 74C922. Appropriate control and data outputs of the decoder 402 are fed to the like-designated terminals of the microcomputer 100 as indicated in FIG. 10 and FIG. 6A. Additionally, a suitable liquid crystal display element 404 is driven by a pair of suitable liquid crystal display driver components 406 and 408, which in the illustrated embodiment comprise components of the type generally designated HLCD438A. In the illustrated embodiment, the display 404 comprises an eight-digit display with decimal points and colons. The data and other control inputs of the two display driver components 406 and 408 are driven from the like-designated terminals of the microcomputer 100 as indicated in FIG. 10 and FIG. 6A.

Referring briefly to FIG. 11 a suitable voltage supply circuit for providing regulated DC voltages at desired levels to the various circuit components thus far described is illustrated. Briefly, the power supply includes variable voltage regulators 500, 502 and 504. In the illustrated embodiment the regulators 500 and 502 are each of the type generally designated 317 and are positive voltage regulators providing respectively +5 and +13.5 volt regulated DC outputs. Regulator 504 is a negative voltage regulator of the type generally designated 337 and provides a -13.5 volt regulated DC output. Additionally, the positive and negative 13.5 volt regulated outputs of the components 502 and 504 are fed to a further voltage regulator component 506. In the illustrated embodiment this latter regulator 506 comprises an integrated circuit component of the type generally designated MC1468L and provides regulated positive and negative 10 volt DC outputs.

In operation, the microcomputer 100 is programmed to control a predetermined sequence of operation to receive the various signals produced by the circuit of FIGS. 7A and 7B. Initially, when the test operation is begun by an operator, the product to be tested is indicated by selection of one of the "product" switches 117 and this selection is indicated by the energization of the corresponding one of the product selection indicator LED's 119. Thereupon, the microcomputer 100 receives the output signal from the circuit of FIGS. 7A and 7B before a sample of material has been introduced into the apparatus. This output signal from the circuit of FIGS. 7A and 7B is received both with the reference resistor 217 switched into the circuit and switched out of the circuit, under the control of the REFR output of the microcomputer 100. Following reception of these signals, the microcomputer 100 causes an appropriate "insert sample" message to be displayed in the characters 109 of the display 14.

Thereupon, the sample cylinder 20 filled with a sample of material to be tested is inserted into the apparatus as described above. The sensor circuit of FIG. 8 verifies that the sample container or cylinder is properly filled to the desired level (at or sufficiently near the line 60 thereon as described above). If the container is not properly filled a suitable error signal is given on the display characters 109 of the display panel 14. When a properly filled sample tube has been inserted in the machine, the temperature reading is initially taken by manipulation of the data temperature switch 119 to the temperature position. Thereafter, the microcomputer 100 again receives the signals provided from the output of the circuit of FIGS. 7A and 7B with the sample present in the apparatus. Once again, these signals are received both with the reference resistor 217 switched into the circuit and switched out of the circuit.

From the foregoing, it will be seen that the microcomputer obtains readings with the sample both present and absent and the reference element or resistor 217 both in circuit and out of circuit. Hence, the microcomputer 100 is programmed to calculate the fat content of the sample based upon all of the readings, by taking appropriate difference values. It will be appreciated that this process substantially eliminates many sources of errors such as gain errors, drift, etc., throughout the circuitry illustrated and described hereinabove.

In order to provide a complete disclosure of a preferred embodiment of the invention, an exemplary program for the microprocessor 100 is produced on the following pages. ##SPC1## ##SPC2## ##SPC3## ##SPC4## ##SPC5## ##SPC6## ##SPC7## ##SPC8## ##SPC9## While the invention has been described herein with reference to a preferred embodiment, the invention is not limited thereto. Those skilled in the art may devise various changes, alternatives and modifications upon reading the foregoing description. The invention includes such alternatives, changes and modifications insorfar as they fall within the spirit and scope of the appended claims.