AC Resistance Measuring Instrument

This invention relates to measuring instruments and more particularly to an instrument for remote measuring of AC resistance over long lines.

The control and study of large irrigation systems involves monitoring changes in moisture content of soil in a field under test. This is generally accomplished by using soil moisture test cells which are located at different points in the field under test. The test cells behave as varying resistance in series with varying capacitance with a change in soil moisture, and variations in soil moisture content is monitored by periodically measuring the impedance, or AC resistance, of each test cell. The test cells are comprised of two stainless steel grid cylinders, one centered inside the other, forming plates to which an AC excitation signal is applied for measuring the impedance. The cost of manually connecting an instrument to individual moisture cells at each test location is prohibitive when surveying large areas. Moreover, measuring the resistance of the test cells on an individual basis requires that a technician walk through the field under test, and it is possible that other test arrangements may be disturbed, adversely affecting the reliability of the test results.

Measuring instruments have been proposed for the purpose of remote measuring of the AC resistance of soil moisture test cells. One such instrument employed a balanced bridge technique to compensate for line impedance. However, both resistance and capacitance balancing were required to achieve a null, and false nulls were possible when the approximate capacitance was not known. Another instrument, designed to compensate for the influence of excitation applitude, series resistance and excitation frequency, employed a technique for rectifying and averaging measured AC resistance. However, this instrument provided no compensation for line capacitance. Neither one of these instruments performed entirely satisfactory.

Therefore a need exists for a portable instrument capable of measuring AC resistance over long lines, typically hundreds of feet in length, and providing reliable readings of the resistance measured.

The present invention provides an auto-ranging AC resistance measuring instrument with line capacitance compensation for measuring the impedance, or AC resistance, of a device, or circuit, over long lines, which may be hundreds of feet in length, and providing a numerical display of the impedance measured. The instrument is a battery-operated, portable unit, suitable for field use.

The measuring instrument comprises a signal generating means for generating an AC excitation signal which is applied to the device through the line which connects the device to the instrument. A monitoring circuit means provides an output signal corresponding to the voltage across the load, including the line and the device, and a signal processing means samples and averages this output over a period of time to provide an output which is indicative of the impedance, or AC resistance, of the device and causes the value of the resistance measured to be displayed on a numerical display.

In accordance with the invention, which is described with reference to measurement of the impedance of soil test moisture cells, during each measurement cycle, the signal processing means provides an auto-ranging function by controlling a range resistance network to connect resistance in series with the load as a function of the load voltage measured. The value of the series range resistance is selected, automatically, to maintain the amplitude of the load voltage within a desired range. The signal processing means also controls a capacitance compensating network to connect capacitance in parallel with the series range resistance to enable the line capacitance to be "pre-charged" so as to minimize distortion of the excitation signal. A symmetrical square wave excitation signal is used to reduce the accuracy requirements of the compensating capacitance.

In providing the auto-compensating function, the signal processing means, by way of the monitoring circuit means, monitors the wave shape of the load voltage and causes binary weighted capacitors to be added incrementally, in parallel with the range resistance until the slope of the load voltage wave form becomes zero or slightly negative, indicative that line compensation has been achieved. One advantage of this technique is that only compensating capacitance need be inserted in parallel with the series range resistance, a technique that is simpler than standard bridge "null" techniques and makes auto ranging and auto-compensating more economically feasible.

In accordance with a feature of the invention, the signal processing means comprises a microprocessor operating under program control to enable the signal generating means to generate its excitation signal, to analyze the signal output of the monitoring circuit means and to control the range resistance and compensating capacitance networks to achieve the desired compensation.

During each measurement operation, the first of five ranges is selected and an excitation signal is applied to the moisture cell under test. The values of a plurality of samples are averaged, and the last value is compared with an upper limit established for range one. If the measured value is below this limit, the averaged data are displayed. However, if the measured value is above this limit, then, the next higher range, range two, is selected by increasing the range resistance and another measurement cycle is initiated.

If the measured value exceeds a second, higher limit established for range two, range three is selected, the range resistance is increased, and a further measurement cycle is initiated, and so on, until the measured impedance is below the upper limit for the selected range.

Ranges one and two are used for relatively low impedances 50K ohms or less, where line capacitance is not a factor in measuring the impedance of the soil moisture cell under test. For higher impedances, i.e. when ranges three through five are used, line capacitance becomes a factor in the measured reading, causing distortion of the square wave signal applied to the load. Capacitance is added in parallel with the range resistance, a few hundred picofarads at a time, until the load voltage waveform once again approximates the waveform of the square wave excitation signal, indicating compensation has been achieved. The load voltage is sampled near its leading and trailing edges in both positive and negative half cycles, thereby offsetting any errors that may be introduced by the electronic circuitry or moisture cell polarization.

In accordance with a further feature of the invention, the battery voltage is automatically tested at the start of each measurement cycle. If the battery voltage becomes less than, or greater than, selected high and low limits, the measurement cycle is terminated, and a suitable indication is displayed on the display unit.

FIG. 1 is a view of the AC resistance measuring instrument provided by the present invention;

FIG. 2 is a block diagram of the measuring instrument shown in FIG. 1;

FIG. 3 is a partial schematic circuit and block diagram of the circuits of the measuring instrument;

FIG. 4 illustrates typical output voltage levels for various levels of compensation;

FIG. 5 is a control firmware hierachy block diagram; and

FIGS. 6-8 are a flow chart illustrating the operation of the instrument.

Referring to FIG. 1, the impedance or AC resistance measuring instrument is a portable, self-contained, battery operated unit. The instrument includes a housing 10 which encloses the circuits of the instrument as well as a rechargable battery pack which energizes the circuits. A front panel 11 of the instrument mounts a pair of terminals 12 by which a device or circuit, the impedance of which is to be measured, is connected to the instrument. A push-button switch 14, when operated, enables the circuits of the instrument to measure the impedance of the device or circuit connected to terminals 12, and display the measured value on a digital display 16 located on the panel 11. A run indicator 27 flashes periodically while the readout 16 is blanked during a pending measurement.

For purposes of illustration, the measuring instrument is described with reference to an application for measuring the impedance or AC resistance of soil moisture cells which serve as moisture sensors in the control and/or study of a large irrigation system. The moisture test cells are commercially available, or easily constructed and accordingly are not shown in detail. One example of a moisture test cell suitable for this purpose comprises two stainless steel grid cylinders, one centered inside the other. The cylinders are separated by gypsum which absorbs moisture at the same rate as do plants. The moisture cell has two terminals each connected to a different one of the grid cylinders. The moisture cells are set in the ground at various depths from six inches to a few feet down. Each soil moisture cell behaves primarily as a resistance in series with a capacitance, both of which vary in accordance with changes in the amount of moisture in the soil.

To simplify the description, the instrument is described with reference to an application for measuring the impedance of a single moisture cell represented by block 32 in FIG. 2. In use, however, the instrument measures the impedances of a large number of such test cells each of which is located at a different location in the irrigation system. The test cells are individually connectable to the measuring instrument which is located at a control location; by way of a switching arrangement (not shown), enabling the impedance of each test cell to be measured.

Referring to FIG. 2 a moisture test cell, represented by block 32, is shown with its terminals G1 and G2 connected to the input terminals 12a and 12b by way of a suitable transmission line 31 which may be several hundred feet in length.

The circuits of the measuring instrument basically comprise a microcomputer 40 including a microprocessor, and associated input/output circuits 41, a program memory 42 and a data memory 44. The program memory 42 stores operating instructions for the microcomputer as well as table look-up data which is used in converting measured data to engineering units. The data memory 44 stores measured data. When the measure push-button 14 is operated to initiate a measurement cycle, the microprocessor is enabled and causes an excitation signal generator 46, embodied as a digital/analog converter, to generate a square wave excitation signal which is applied to the load connected to input terminals 12, including the soil test cell 32 and the transmission line 31. A monitoring circuit 52, embodied as an analog/digital converter, monitors the voltage across the load and provides to the microcomputer, a digital signal corresponding to the value of the load voltage. The microcomputer uses this signal to determine the amplitude and wave shape of the load voltage, and controls a line compensation network 48, which is interposed between the output of the digital/analog converter 46 and the load, to compensate as necessary for the effects of the transmission line 31.

The compensation network 48 includes a series range resistance section 49 and a shunt compensating capacitance section 50. The microcomputer, under program control, automatically selects the values of series resistance and shunt capacitance as a function of the load voltage measured.

The instrument has five ranges which are selected by auto-incrementing under microprocessor control. The ranges are defined as follows:

The series compensating resistance is selected to maintain the peak load voltage within 50% to 90% of the value of the signal generated by the digital/analog converter 46. In each measuring operation, range 1 is selected first, and if the load voltage is not within 50% to 90% of the value of the excitation signal, the next range is selected, and then the next range until the load voltage is within 50% to 90% of the excitation signal. Shunt compensating capacitance is added under microprocessor control whenever ranges 3, 4 or 5 are selected. The composition of the compensation network 48, as well as the auto-ranging and auto-compensation functions, are described in detail hereinafter.

When the auto-ranging and the auto-compensation functions have been completed, the microcomputer, via the analog/digital converter 52, samples the load voltage and averages the samples to provide an output corresponding to the impedance of the load, i.e. the transmission line and the test cell. The impedance of the moisture cell alone can be determined on the basis of previous knowledge of the transmission line impedance.

The microprocessor controls the digital display 16 via associated display drivers 54 to provide a four digit numerical display of the measured impedance.

In one measuring instrument which was constructed, the microprocessor 41 comprised the Type C8085A 8-bit microcomputer and suitable input/output circuits. The program memory 42 comprised a 2K.times.8-bit Type 2716 programmable read only memory, serving as instruction store, and a 1K.times.8-bit Type 2758 programmable read only memory, providing storage for table look-up data. The data storage memory 44 comprised two 256.times.4-bit Type 8561 CMOS random access memories. The digital display comprised a Type 7547 four-digit liquid crystal display unit which provides three digit resolution (except under 100 ohms) and one multiplier digit for readout of AC resistance. The display driver circuits 54 comprised four Type 4056BE LCD drivers. A comparator circuit 36, used for battery test operations, comprised a Type 311 H operational amplifier connected for operation as a differential amplifier. The compensating network 48, the digital/analog converter 46 and the analog/digital converter are shown in more detail in FIG. 3 and discussed hereinbelow.

The circuits of the measuring instrument are energized by a 12 volt rechargable battery source 33 which via DC/DC converter circuits 55 provide voltages at levels of .+-.15 VDC and +5 VDC for the circuits. A power switch 22, which is mounted on the control panel (FIG. 1) is operable to connect the DC/DC converter 55 to the battery source 33. A fuse 31 (FIG. 1), which is connected between the positive terminal of the battery and the power switch 22, affords overload protection for the circuits of the instrument.

The power circuits include a battery charger 34, which is connectable to an AC source via charge switch 24 and a connector 25, mounted on the control panel. The battery charger 34 enables the battery pack to be recharged when the instrument is not in use. An indicator 26 (FIG. 1) illuminates while the power pack is being charged.

Each time a measurement is requested, the comparator circuit 36 compares the battery voltage with a reference voltage and provides a signal at its output 36a indicative of the battery voltage. If the battery voltage is too low, the microprocessor causes the letters LLL to be displayed. Similarly, if the battery voltage is too high, the letters HHH are displayed. In either case, the measurement cycle is denied. The battery voltage may be checked at any time by operating the battery push-button 18 (FIG. 1), located on the panel 11, (FIG. 1) prior to and concurrently with the measure push-button 14 (FIG. 1).

After each measurement operation, the microprocessor circuits are deenergized, and the program memory 42 is switched to a standby mode, i.e. powered down, in order to conserve power. The circuits are reactivated during an initialization operation which occurs each time the measure push-button 14 is operated.

Referring to FIG. 3, which illustrates the compensation network 48 in detail, the microprocessor, the memories and associated input/output circuits are represented by a block 40 which is labelled microcomputer control. The microcomputer communicates with the D/A converter circuit 46 and the A/D converter circuit 52 by way of a data bus 58. The measure switch 14 is connected to an input of the microprocessor over an associated anti-bounce circuit (not shown). A timer circuit 57, which operates asynchronously of the microprocessor clock, generates timing signals which serve as interrupts to the microprocessor to establish excitation frequency and data sampling rates. The function of this timer circuit 57 is described in more detail hereinbelow in connection with the discussion of the manner in which the output waveform is analyzed during the auto-compensation operation.

The digital/analog converter 46 comprises a commercially available type AD561K digital/analog converter circuit 46a and an associated output driver circuit 46b which is a Type 301AN operational amplifier. The microcomputer control provides a multi-bit control word to the digital/analog converter circuit 46a over a data bus 58. However, since only two of the bits are required to enable the digital/analog converter to provide a symmetrical square wave signal at a 15 VDC peak level, only the least significant bit LSB and the most significant bit MSB are extended to the signal inputs of the digital/analog converter, the unused signal inputs being commonly connected to the LSB input, for example.

The range network 49 comprises five resistors R1-R5 which are connectable in series with the output of the D/A converter 46 by way of associated switches SR1-SR5 which are operated under the control of the microcomputer. The switches SR1-SR4 are reed relays which present a substantially open impedance to the output of the D/A converter 46 when all of the switches are unoperated. Each reed switch has an associated driver (not shown) which receives an enabling signal from the microcomputer by way of associated I/O latches (not shown). Switch SR5 may be a solid state switch bus as one section of the commercially available Type AD-1510 DI quad MOS analog switch. A solid state switch may be used because resistor R5, its value of 4 megohms together with the off-resistance of the analog switch, normally presents a virtually open circuit. In one circuit, resistors R1-R5 had values of 1K, 9K, 99K, 1M, and 4M ohms, respectively.

The microcomputer generates outputs which are stored in its output latch circuits and are applied to inputs of the reed switch drivers for operating reed switches SR1-SR4, or to analog switch SR5, to select the desired range at the start of each measurement cycle. Range 1 is always selected first, and switch SR1 is operated to connect resistor R1 in series with the load. If the output voltage is not within a range of 50-90% of the square wave signal generated by the D/A converter 46, then switch SR2 is operated, connecting resistor R2 in series with resistor R1 and the load, thereby selecting range 2. Resistor R1 is connected in circuit for all five ranges to isolate the capacitors C1-C7 from the D/A converter output to assure that a non-capacitive load is presented to the D/A converter 46. To select range 3, switch SR2 is disabled, and switch SR3 is enabled. Similarly, switch SR4 (or SR5) is operated to select range 4 (or 5). The range resistance network together with the load operate as a voltage divider with the series range resistance being increased to "match" higher values of load impedance thereby lowering the voltage at the mounting point i.e. the junction of the series range resistance and the load.

The compensation network 50 comprises seven binary weighted capacitors C1-C7 each having an associated switching device SC1-SC7 represented by switch contacts. Each of the switches is operated under microcomputer control by computer generated outputs, provided over inputs L2-L8, to connect selected ones of the capacitors in parallel with the range resistance selected. Solid state switch devices, such as the commercially available type AD 7510 DI Quad MOS analog switches, are used to minimize power requirements and afford faster switching speeds than provided by the reed switches used in the range network. The slower speed reed switches can be used for range selection because during range selection the range is changed infrequently, i.e. typically two or three times. In one circuit which was constructed, capacitors C1-C7 had values of 500 pfd, 0.001 ufd, 0.002 ufd, 0.004 ufd, 0.008 ufd, 0.016 ufd and 0.032 ufd. respectively.

A switch SC8, which may be a reed switch operated under computer control, normally connects one terminal of capacitors C1 and C2 to the output circuit, thereby enabling capacitors C1 and C2 to be connected in circuit with the range resistance whenever switches SC1 and SC2 are operated. The switch SC8 is operable to connect one terminal of capacitors C5-C7 to the output circuit, and disconnect the capacitors C1 and C2 from the output circuit, thereby enabling capacitors C5-C7 to be connected in circuit with the range resistance. This switching arrangement minimizes the number of capacitors which are connected in the output circuit of the D/A converter circuit to reduce the effect of parallel leakage currents within circuit 50.

The manner in which the microcomputer controls the selection of capacitors during an auto-compensation operation is described with reference to FIG. 4. At impedances over 100K ohms over several hundred feet of transmission line, the uncompensated output signal would look similar to curve 64 shown in FIG. 4. The addition of binary weighted capacitors C1-C7 in series with resistor R1, which together are in parallel with selected ones of the range resistors R2-R5 pre-charge the transmission line at a rate to provide correct compensation.

Generally, the compensated output voltage will approximate the form of the square wave excitation signal, represented by dashed line 61. Over-compensation results in a final voltage, waveform 62, which is too high, whereas under-compensation results in reaching a final voltage waveform 63, which is too low.

The microprocessor determines when the best compensation has been achieved by looking at point A-B, of the positive half cycle of the square wave output, and points A'-B' of the negative half cycle, and adding an increasing amount of compensating capacitance during each measurement cycle. When the voltage levels at points A and B (and A' and B') are equal, i.e. zero slope, then correct compensation has been achieved. It is pointed out that in some instances, zero slope may not be realized in which case a slightly negative slope is indicative of adequate compensation.

Referring again to FIG. 3, the monitoring circuit 52 monitors the output voltage and provides to the microprocessor, via data bus 58, a ten bit digital signal representing the output voltage waveform. The monitoring circuit 52 comprises a high impedance buffer amplifier 52a, such as the Type LM 302H, operating as a voltage follower, and a high speed (25u sec.) A/D converter 52b, such as the commercially available Type AD 571K converter circuit, which digitizes and stores the measured data. The eight lower order bits are supplied to the microprocessor by way of a first I/O latch (not shown) and the two most significant bits are supplied to the microprocessor via a further I/O latch. The junction of buffer amplifier output and the A/D converter input is extended as a monitor point to a BNC connector 29 mounted on the control panel 11 (FIG. 1).

The timer circuit 57 comprises a clock tick oscillator, which operates asynchronously with respect to the microprocessor clock to generate interrupt signals for the microprocessor at a 1.6 KHZ rate. These interrupt signals provide reference for timing in generating the period of the square wave excitation signal and establish data sampling rates which enable the microprocessor to sample the load voltage near the leading and trailing edges of the positive and negative half cycles of the square wave signal.

The output voltage is sampled synchonously with the time circuit 57 and samples are accrued at a rate of eight samples per half cycle during a measurement cycle For ranges one and two, the frequency of the excitation signal is 100 Hz, and for ranges three through five, a 50 Hz excitation signal is used. Samples are taken at the leading and trailing edges of each half cycle under microprocessor control.

The output voltage samples are used to determine the total impedance, including the impedance of the line and the moisture cell under test, by the equation: ##EQU1## where: Eo is the final output voltage (points B, B')

Rs is the series range resistance

Ea is the peak output voltage applied, and

Zm is the measured impedance

This relationship is implemented using a look-up table stored in the read only memory 42.

The impedance of the moisture cell alone can only be determined by previous knowledge of the transmission line impedance. This is calculated at time of installation of the system. The equation for moisture cell impedance becomes ##EQU2## where: Z1 is the moisture cell impedance

Z2 is the transmission line impedance

Zm is the measured impedance (Z1 Z2)

The effects of moisture cell polarization and hardware offset voltages are minimized by sampling both the positive and negative slopes of the output waveform.

Referring to FIG. 5, the control firmware subprogram hierachy is illustrated to provide an overview of the system program, a program listing for which is provided in appendix I. The subroutines include initialization (BEGIN) 71 starting at line 68; battery voltage scanner (BUSCAN) 72 beginning at line 984; auto-ranging resistance measurement (MEASUR) 73 beginning at line 156; and display scanner (DISPLY) 74 beginning at line 890. A mode and status scanner (STSCAN) 75, beginning at line 848, scans the status of panel mounted switches as well as the battery test flag, and a time keeping subroutine (IENTR) 76 generates the interrupt signals, at a rate of 0.625 milliseconds, for the microprocessor.

The auto-ranging resistance measurement subroutine includes resistance range routine (MAGAIN) 77, starting at line 194, which controls the incrementing of the resistance range, and a compensating capacitance controller (CAPINR) 78, beginning at line 719, which controls the connection of the compensating capacitance into the circuit. A stabilization routine (STABLS) 79, beginning at line 494, provides the delays during the measurement cycle to permit stabilization of the measured voltage before data is used. An outside limit check routine 80, starting at line 1024, determines when the measured voltage is out of range, and a binary to BCD conversion routine (BNBCT) 81, beginning at line 1046, controls the conversion of the binary data output of the A/B converter to decimal. The voltage/resistance lookup table is provided beginning at line 1096, and the ADC voltage to battery voltage table begins at line 1191.

FIGS. 6 7, and 8 illustrate a flow chart for the program. The program consists of four basic operations namely: initialization; battery voltage check; autoranging measurement, including range selection, line compensation, and resistance calculation, and display.

Referring first to FIG. 6, the program functions are initiated in block 91 in response to the operation of the measure push-button 14 (FIG. 1). The initialization includes activating the circuits which are normally powered down between measurements. The program at block 92 causes the display to be blanked, and then at block 93, the program pauses for 300 milliseconds, allowing the circuits to stabilize after application of power.

At decision block 94, the status of the battery voltage comparator circuit 36 (FIG. 2) is read, and if the battery voltage is too low, the program advances to block 95 to cause the letters LLL to be displayed on display 16 (FIG. 1) and at block 96, halts the program, terminating the measurement cycle. If the battery voltage is above the minimum level, then at block 97-99, the status of the battery voltage push-button 18 (FIG. 1) is read to determine if this is a measurement cycle of a battery check operation. If the switch 18 is operated, then the battery voltage is read and displayed at block 99. If the battery voltage is too high, the program advances to block 100 (FIG. 8), and causes the letters HI to be displayed. This operation is provided both for battery test and during resistance measurement cycles.

Assuming that battery test switch 18 has not been operated, then after the battery voltage check operation, the program proceeds to the auto-ranging measurement operations. The first aspect of the auto-ranging operation is the selection of the range, and at block 101, range 1 is selected automatically at the beginning of each measurement operation. This causes resistor R1 to be connected in series with the load for the first measurement cycle, and for subsequent cycles, resistors R2, R3, etc. are connected in series with load until the correct resistance is found. At decision block 102, it is determined whether ranges 3, 4 or 5 have been selected and at blocks 103 and 104, the appropriate excitation signal frequency is selected as a function of the range presently selected. A 100 Hz signal is used for ranges 1 and 2, and a 50 Hz frequency signal is used for ranges 3-5.

Referring to FIG. 7, for all ranges, the program waits for four stabilization cycles at block 105 and then advances to block 106 to read eight samples during each half cycle, (a total of sixteen samples) during the final ninth cycle.

The program advances to block 107 where a test is made to determine if range 1 is selected. Also, the sixteen samples are averaged and the last value read is compared with the upper limit 5K ohms for range 1 to determine whether or not the signal is over range. Assuming that range 1 is selected and that the signal is not over range, then a block 108, the sixteen samples are averaged and displayed. If the upper limit for range 1 is exceeded, that the program returns to block 101 (FIG. 6) and the resistance range is incremented by one. The microcomputer causes switch SW2 (FIG. 3) to be operated, connecting resistor R2 in series with the load and resistor R1.

The program proceeds through blocks 102-107 as before, and since range 2 is now selected, the program advances to block 109. Assuming that the last value read is less than 50K ohms, the upper limit for range 2, then the program advances to block 110 where the last four readings of each half cycle are used for averaging and display. If, on the other hand, the last value read is greater than 50K ohms, then at block 109 the program returns to block 101 and selects range 3 by disabling switch SW2 and enabling switch SW3 to connect resistor R3 in series with the load in place of resistor R2.

When range 3 (or ranges 4 or 5) is selected, then at block 102, the program proceeds to block 104 to cause the frequency of the excitation signal to be changed from 100 Hz to 50 Hz. The program proceeds through blocks 105-109 and at block 111 the program determines that range 3 has been presently selected and uses the data read to determine whether or not the reading exceeds 500K ohms, the upper limit for range 3. Assuming that the value read is less than the upper limit for range 3, than at blocks 111-113, the program provides the auto-compensation function, adding an increasing amount of line compensation capacitance across the series limiting range resistor R3 until the positive waveform slope is compensated to a point where it becomes zero or a slightly negative slope. As described above with reference to FIG. 4, the slope of the excitation signal waveform is determined by looking at samples of the output voltage waveform near its leading and trailing edges in both positive and negative half cycles. The slope of the waveform is determined by averaging the absolute value of all sixteen samples. The average must be greater than or equal to the average of the last set of samples. If at any point along the way to compensating for line capacitance, the final reading exceeds 500K ohms, then the program returns to block 101 to select the next higher range. During the outer compensation operation, the microcomputer operates switches SC1-SC7 to initially increase line compensating capacitance in increments of 500 pf. If proper compensation is not achieved by the time capacitors C1-C4 are all connected in parallel across the range resistance, then switch SC8 is operated, disconnected capacitors C1 and C2 from the circuit, and enabling capacitors C5-C7 to be connected in parallel with the range resistance when their associated switches SC5-SC7 are operated under microcomputer control.

At block 112, the program determines when proper compensation has been achieved and then advances to block 110 where the last four samples for each half cycle, (eight samples) are averaged and displayed. If at block 111 the program determines that the final reading exceeds 500K ohms, then program returns to block 101 and selects range 4, causing resistor R4 to be connected in series with the load.

When range 4 is selected, the program operates in a manner identical to that when range 3 is selected, providing auto-compensation by way of blocks 114-116. If the final reading in any measurement cycle exceeds 2M ohms, the fifth range is selected at block 101.

Referring now to FIG. 8, the program operates for range five in a manner identical to that for ranges 3 and 4, with blocks 117-119 providing auto-compensation except that if the final reading in any measurement cycle is equal to or greater than 10M ohms, then block 120 terminates the measurement cycle and block 100 causes the message "HI" to be displayed to inform the user that either the AC resistance is to high or line capacitance is to great, or both. When proper compensation is achieved, then at block 121, the program averages the last four samples each half cycle and displayes the averaged data. ##SPC1## ##SPC2## ##SPC3## ##SPC4## ##SPC5##