Line Isolation and Interference Shielding for a Shielded Conductor System

This invention relates generally to the fields of high frequency electromagnetic interference shielding an A.C. power isolation. It is particularly directed to the shielding of high frequency shielded conductor systems, such as coaxial cables, from electromagnetic interference and the simultaneous isolation of such conductor systems from sources of A.C. power. The 75 ohm coaxial cable input to a television tuner is a prime example of one type of shielded conductor to which such shielding and isolation is directed.

Television receiver manufacturers are currently required by Underwriters Laboratories (U.L.) to doubly isolate exposed metal parts from the A.C. line which powers the receiver. For example, the 300 ohm twin lead terminals usually situated on the rear of the receiver's cabinet are required to be separately isolated. Such isolation is intended to doubly insulate a consumer from accidental shock which he might otherwise receive either from contact with the exposed terminals or with the metal "rabbit ear" antenna to which such terminals are sometimes connected.

Conventionally, television receivers also include an exposed connection for a 75 ohm coaxial cable input to the receiver's VHF tuner. No U.L. requirement presently exists providing for double isolation of the coaxial input, evidently because the technology has not been available to television manufacturers to enable them to provide such isolation while simultaneously affording acceptable television reception.

The problem which arises in connection with the 75 ohm coaxial input is that conventional techniques for isolating the coaxial input from the A.C. line tend to permit ambient high frequency electromagnetic interference signal to couple with the field within the cable, and thus to interfere with the desired signal propagating inside the coaxial cable.

For example, one prior approach utilizes conventional capacitors coupling the coaxial cable with the tuner input to A.C. isolate the cable from the tuner. While the isolation thus achieved is satisfactory, the field within the cable is inadequately shielded from electromagnetic interference.

A more recent isolation technique, described in copending application Ser. No. 184,720, filed Sept. 8, 1980, employs a feed-through or tubular type capacitor in the cable for A.C. isolation. The latter arrangement does provide the required degree of A.C. line isolation but, in fields of strong ambient electromagnetic interference, its shielding effect is less than perfectly satisfactory.

The shielding problems mentioned above may be particularly evident where the coaxial cable, connected to the 75 ohm input, carries a CATV signal. If the cable includes an A.C. isolator which is an inadequate electromagnetic interference shield, strong co-channel ambient broadcast fields will not be adequately shielded from the field within the coaxial cable and will produce strong co-channel interference.

For the reasons stated above, presently available A.C. isolators have not proven adequate where electromagnetic interference shielding is of importance.

It is a general object of the invention to provide a method and apparatus for isolating the shield of a shielded high frequency conductor system from low frequency A.C. power in such a way that the desired field within the cable is shielded from ambient high frequency electromagnetic interference.

It is another object of the invention to provide such isolation and shielding for a shielded conductor system adapted to carry a television signal to the tuner of a television receiver.

The objects stated above and other objects of the invention are more particularly set forth in the following detailed description and in the accompanying drawings, of which:

FIG. 1 illustrates a coaxial cable having conventional capacitive A.C. line isolation;

FIG. 2 illustrates a cable-isolator assembly in accordance with the invention;

FIG. 3 is a lumped-element equivalent circuit diagram useful in explaining the operation of the embodiment shown in FIG. 2;

FIGS. 4-6 illustrate alternate embodiments of the isolator assembly shown in FIG. 2;

FIG. 7 illustrates the interference attenuation characteristics of a conventional discrete isolator;

FIG. 8 illustrates the interference attenuation characteristics of the isolator assembly shown in FIG. 2;

FIG. 9 is a cross-sectional view of another isolator in accordance with the invention in which one of the dielectric elements is connected with an inductance to form a resonator;

FIG. 10 is a cross-sectional view of the type of isolator shown in FIG. 9, but having additional ferrite and dielectric elements;

FIG. 11 illustrates the interference attenuation characteristics of the isolator shown in FIG. 10;

FIG. 12 is a cross-sectional view of another embodiment of a FIG. 10 type isolator;

FIG. 13 depicts the shielded conductor of FIG. 12 as seen in an unrolled or flattened condition and the manner in which an inductive finger may be formed therein;

FIG. 14 illustrates another method of forming the inductive finger in the shielded conductor;

FIG. 15 is a front view of an alternate embodiment of an annular dielectric element, its metallization pattern, and the manner in which the metallization pattern is coupled to an outer conductor to form a resonator;

FIG. 16 is a perspective view of the dielectric element shown in FIG. 15;

FIG. 17 is an idealized and abbreviated plot of impedance versus frequency for the type of resonator shown in FIG. 15;

FIG. 18 is a cross-sectional view of an isolator assembly which includes the type of resonator shown in FIG. 15; and

FIG. 19 is a cross-sectional view of an isolator assembly which includes two resonators of the type shown in FIGS. 15 and 16.

Referring to FIG. 1, a coaxial cable 10 is shown which may be used for carrying a television signal to the tuner of a television receiver. The cable 10 has an inner conductor 12 disposed coaxially within an outer conductor 14. The rightmost end 16 of the cable may be coupled to a signal source and the leftmost end 18 may be coupled to the input of a television tuner.

Conventionally, the tuner may be isolated from the A.C. line which powers the receiver. To doubly isolate the end 16 of the cable from the A.C. line, it has been proposed to capacitively couple the ends 16 and 18 of the outer conductor 14. This prior approach is indicated schematically by capacitors 20 and 22 disposed in the cable's outer conductor. The capacitors 20 and 22 are selected to provide a high impedance at the low frequencies associated with the A.C. line, thereby to further isolate the end 16 of the cable from the line voltage. The inner conductor 12 may also be decoupled from the A.C. line by a capacitor (not shown).

Although the isolation effected by the technique shown in FIG. 1 is satisfactory, the simple capacitive decoupling of the outside conductor can cause an intolerable increase in electromagnetic interference, particularly when a local signal is broadcast on the same frequency as a CATV signal carried by the cable.

FIG. 2 shows a preferred embodiment of one type of isolator according to the invention. A shielded conductor system in the form of a coaxial cable 24 includes an inner conductor 26 and an outer conductor 28. The cable may include a leftmost portion 30 whose outer diameter is greater than the outer diameter of the rightmost portion 32 such that a portion 34 of the larger diameter outer conductor overlaps the smaller diameter outer conductor. The space defined by such overlap constitutes a gap or interruption in which dielectric and magnetically absorptive material is situated for purposes of shielding and line isolation.

In the illustrated embodiment, the annular, cavity-like interruption thus created holds two discrete elements of dielectric material 36 and 38 separated by an element of magnetically absorptive material 40. Each such element is annular and has a central opening to surround the smaller diameter outer conductor. The elements 36, 38 and 40 may be stacked one against the other and aligned coaxially of the cable as illustrated.

With this arrangement, the dielectric elements 36 and 38 create a capacitive coupling across the gap between the large and small diameter portions of the outer conductor to isolate the rightmost portion 32 of the outer conductor from the leftmost portion 30. Hence, any A.C. line voltage applied to the leftmost portion 30 is inhibited from reaching the rightmost portion 32. In addition, the capacitances formed by the elements 36 and 38 co-operate with the element 40 to shield the field inside the cable 24 from ambient electromagnetic radiation, as described hereinafter.

The magnetically absorptive element 40 serves to absorb electromagnetic interference not bypassed by the capacitive effect of elements 36 and 38, without any substantial absorption of the desired field within the cable.

To more fully explain the shielding effect achieved, reference is made to FIG. 3 which shows an equivalent circuit diagram of a two port which may be placed between the cross sections AA (input port) and BB (output port) of FIG. 2. The source I represents the current on the outer surface of the outer conductor induced in the vicinity of the cross section AA by the ambient interfering signal. The source E represents the desired signal to be carried by the cable, the resistor R1 represents the nominal output impedance of the source E (75 ohms), and the resistor R2 represents the nominal input impedance (75 ohms) of a television tuner.

The resistor R3 represents the equivalent series resistance (100 ohms, for example) of the magnetically absorptive element 40, the capacitor C1 represents the capacitance due to the effect of the dielectric element 36, and the capacitor C2 represents the capacitance due to the effect of the dielectric element 38. Each capacitor C1 and C2 may, by way of example, have a value of about 2000 picofarads.

At typical television frequencies, the impedance of the capacitors C1 and C2 is much less than the impedance of any of the resistors in FIG. 3, Hence, the capacitor C1 shunts the desired signal from source E away from the resistance R3 and toward the input impedance of the tuner. Consequently, the magnetically absorptive material represented by R3 does not substantially absorb any of the desired signal.

The capacitor C2 acts to shunt the current I so that the interference current does not develop a substantial corresponding voltage in R2 (the tuner input impedance).

Because the capacitor C2 has only a finite capacitance, not all the current I will be shunted. However, capacitors C1 and C2 cause the residual electromagnetic interference to be absorbed by the magnetically absorptive material (R3).

It should be mentioned that any magnetically absorptive material will also produce an equivalent and frequency dependent inductance which is in series with its equivalent resistance. Such inductance may help to suppress interference at lower frequencies, but it is not very desirable at higher frequencies. Hence, the magnetically absorptive material should be selected to maximize interference suppression at the frequencies of interest for a particular application.

Referring again to FIG. 2, the arrangement shown therein has been found to provide exceptional shielding from electromagnetic interference while simultaneously providing isolation from the line voltage. The dielectric elements 36 and 38 may be of any suitable dielectric material preferably having a high dielectric constant of several thousands to provide a capacitance of at least 2000 picofarads. Barium titante is one example of such dielectric material.

The element 40 is made of a magnetically absorptive material whose equivalent series resistance is as high as possible at the frequencies of interest for best absorption of electromagnetic interference. A ferrite material having an equivalent series resistance of about 100 ohms has been found to be acceptable for use at television frequencies. Such a ferrite is available from Fair-Rite Products Corp., Wallkill, N.Y., referred to as material number 43 or 64.

In constructing the isolator, the dielectric elements 36 and 38 may be silver plated inside and outside and soldered to the outer conductor 28 on the inside and to the outer conductor 30 on the outside. The magnetically absorptive element 40 may be in the form of a ferrite bead disposed loosely between the dielectric elements and need not be in physical contact with the cable's outer conductor. It is thought that greater A.C. line isolation may result if no such contact is permitted, particularly in the case where ferrite materials with a high D.C. specific conductance are used.

It will be appreciated that the isolator-cable combination may be used in applications other than with television tuners. However, when the cable 24 is designed to carry a signal to a television tuner, the interruption or cavity described above need not be completely disposed in the cable alone. For example, in FIG. 2, the leftmost portion 30 of the cable (the part of larger diameter) may actually be an input connector to a television tuner. In that case, the larger diameter portion of the connector may be extended over the smaller diameter cable so that an area of axial overlap exists as shown, with the dielectric and magnetically absorptive material disposed in the gap defined by the area of axial overlap. Hence, when an interruption is referred to herein as being in the outer conductor of a cable, it is to be understood that such terminology is meant to also include an interruption between the outer conductor of the cable and a corresponding connection to a tuner input or corresponding structure. In fact, the required isolation and shielding may be effected by disposing the interruption at any practical location in a coupling path between the outer conductor of the cable and the input to the tuner or corresponding structure.

Such a connector and cable as shown in FIG. 2 may be disposed within a television receiver's cabinet. In that case, the cable itself need not be flexible as is the case with conventional coaxial cable. Instead, the cable may be constructed of conductive pipe having a center conductor. Such a pipe will be understood to be the equivalent of a coaxial cable, wherefore, references herein to a coaxial cable or a shielded conductor are intended to be inclusive of such pipes.

In some instances, the interruption may be implemented without the use of either a coaxial cable or a conductive pipe. Instead, the interruption may be placed within a connector which is attached directly to a television tuner or corresponding structure. Hence, references herein to a shielded conductor are meant to include such connectors and their equivalents.

The isolator of FIG. 2 comprising the elements 36, 38 and 40 is illustrated as employing only one ferrite or magnetically absorptive element disposed between a pair of dielectric elements. However, additional dielectric and ferrite elements may be used in an alternating sequence, as shown in phantom at 138 and 140, respectively. In the illustrated embodiment, the first element on the inside (element 36 in FIG. 2) is a dielectric element so that no losses are introduced into the desired signal path. The first element on the outside (element 38 in FIG. 2) may be either a dielectric element or a magnetically absorptive element, the former case being more effective.

There are several alternatives for the design of an A.C. line isolator, the construction of which depends on the main direction in which the electromagnetic interference signal within the isolator is forced to propagate (radially or axially). The construction shown in FIG. 2 illustrates a case in which the interference signal propagates axially and the dielectric-ferrite pairs are distributed axially.

FIG. 4 illustrates an isolator in a coaxial cable for radially propagating interference signals and having radially distributed dielectric-ferrite elements. As shown, the cable 24a has an inner conductor 26a and an outer conductor 28a. The latter conductor is divided with upturned edges or radial flanges arranged vis-a-vis to form a gap or interruption 42a in which dielectric elements 36a and 38a are separated by a ferrite or other type of magnetically absorptive element 40a so that the dielectric and magnetically absorptive elements are sandwiched between the flanges and concentrically arranged such that the alternating sequence of elements is in a direction radial to the cable. Again, as in the FIG. 2 embodiment and other embodiments to follow, a greater number of dielectric and magnetically absorptive elements may be employed in alternating sequence in applications where greater performance is desired in spite of the necessarily higher consequent cost.

Referring to FIG. 5, an alternative design is shown for the case in which the interference signal propagates axially and the dielectric-ferrite pairs are disposed radially. In this design, the cable 24b has an inner conductor 26b and an outer conductor 28b, the latter being separated into two parts (left and right, as shown). The ends of the separated parts are interleaved so as to provide a total of at least three spaces between the interleaved parts. A first space contains a dielectric element 36b, a second space contains a magnetically absorptive element 40b, and a third space contains another dielectric element 38b.

Another embodiment is shown in FIG. 6 in which the interference signal propagates radially and the isolator elements are distributed axially. Again, an outer conductor 28c of the cable 24c is separated into two parts as shown. The separated parts of the outer conductor are interleaved to provide at least three spaces. A dielectric element 36c is disposed in a first space, a magnetically absorptive element 40c is disposed in a second space, and another dielectric element is disposed in the third space.

In FIGS. 2 and 4-6, the dielectric and ferrite elements are shown as abutting each other. The reasons for this preferred construction are twofold.

First, maintaining the ferrite and dielectric elements in an abutting relationship eliminates air gaps between them. Large air gaps, if present, represent inductances which can provide parasitic resonances at some television frequencies. Consequently, less attenuation of electromagnetic interference can occur.

Second, maintaining the dielectric elements immediately adjacent a sandwiched ferrite element tends to hold the ferrite element in its proper position.

The cable shielding and isolation technique described above has been found to provide satisfactory isolation and superior shielding from electromagnetic interference. In fact, measurements in television receivers exposed to strong ambient fields have shown that an isolator-cable assembly of the type shown in FIG. 2 provides interference suppression which is approximately equivalent to the interference suppression provided by a singly isolated, fully shielded cable, the primary limitation on electromagnetic interference pickup being the construction and quality of shielding built into the tuner.

There are circumstances in which strong ambient fields exist, particularly in the low UHF television band (around 50-60 megahertz) and/or in the FM band. In these conditions, it is desirable for the isolator to exhibit very good RFI (Radio Frequency Interference) attenuation characteristics, particularly at these relatively low frequencies. Of course, good RFI attenuation should also be provided at frequencies up to and above about 175 megahertz.

Referring to FIG. 7, the curve 50 illustrates the RFI attenuation characteristics of a conventional isolator. As shown, good RFI attenuation is achieved at about 25 megahertz, but the attenuation decreases somewhat at around 100 megahertz and decreases even further at frequencies above 175 megahertz.

FIG. 8 illustrates the RFI attenuation characteristics of an isolator of the type shown in FIG. 2. As indicated by the curve 51, RFI attenuation increases monotonically as a function of increasing frequency to provide very good attenuation at high frequencies and reasonable attenuation at low frequencies.

To provide even greater attenuation at lower frequencies, particularly in the 50 to 60 megahertz range (the low VHF band) in accordance with another aspect of the invention, an inductance is provided within the shield's interruption for coacting with at least some of the dielectric material therein to form at least one resonator. Preferably, the resonator establishes a condition of series resonance for frequencies in the low VHF band to increase RFI attenuation at those frequencies.

One manner of providing such a resonator is illustrated in FIG. 9. As shown, a shielded conductor having an inner conductor 54 and a shield 56 is mated with any suitable conductive means such as a larger diameter shield 58 to form an interruption or area or axial overlap 60. The shield 56 and the inner conductor 54 may receive an RF input, and the shield 58 and the inner conductor may carry the RF input to a television tuner or the like.

Disposed within the interruption is an annular dielectric element 62, an annular magnetically absorptive element 64, and another annular dielectric element 66. Adjacent elements abut each other and are arranged concentrically around the shield 56. The elements 62 and 66 each have conductive coatings (not shown) on their inner and outer perimeters so that their inner perimeters may be soldered to the shield 56 and the outer perimeter of the element 62 may be soldered to the shield 58.

The dielectric element 62 and the magnetically absorptive element 64 function in the same manner as the dielectric and magnetically absorptive elements described previously. In this embodiment, however, the dielectric element 66 has an outer diameter which is smaller than the outer diameter of the element 62 so that its outer conductive coating is not in physical contact with the shield 58.

A conductive finger 68 (which may be a part of the shield 58) extends into the interruption to make an electrical connection between the shield 58 and the outer conductive coating on dielectric element 66. The length and width of the finger 68 and the dielectric constant of the element 66 are selected so that the inductance provided by the finger 68 coacts with the dielectric element 66 to form a resonator which exhibits series resonance in the low band of VHF frequencies (50-60 megahertz). Consequently, additional RFI attenuation is provided at these frequencies without substantially reducing the attenuation provided at higher frequencies.

When the dielectric element 66 is selected to exhibit a capacitance of 1.5 nanofarads and the finger 68 is selected to exhibit an inductance of 7 nanohenries, the resonator is series resonant at approximately 50 megahertz. The attenuation characteristics of that isolator are depicted in FIG. 11.

As shown by the curve 70, a local attenuation maximum is obtained at about 50 megahertz, and the attenuation keeps increasing with increasing frequency. Thus, the isolator of FIG. 9 provides very good RFI attenuation over a wide frequency range.

Isolators of the type shown in FIG. 9 are not limited to three elements. As shown in FIG. 10, for example, an isolator may include dielectric elements 62a and 66a sandwiching a magnetically absorptive element 64a, and an inductive finger 68a, all of which function in the manner described previously. Abutting the element 66a is another magnetically absorptive element 72 followed by another dielectric element 74. The inclusion of the elements 72 and 74 further increases RFI attenuation. The use of an additional magnetically absorptive element at 76 and another dielectric element at 78 will increase RFI attenuation even further. However, an additional increase in the number of dielectric and magnetically absorptive elements has a reduced effect on the rate at which RFI attenuation increases, the reason being that the total capacitance should not exceed 4 ramofarads.

In the embodiments of FIGS. 9 and 10, the dielectric part of the resonator was made physically smaller than the other dielectric elements to avoid direct contact with the large diameter outer shield. Another manner in which this result may be obtained is illustrated in FIG. 12.

As shown, elements 62b, 64b, 72b and 74b are concentrically disposed around the shield 56b in the same manner as depicted in FIG. 10. However, the resonator includes a dielectric element 80b which is of the same physical size as the other dielectric elements, and the shield 58b is formed so as to avoid direct contact between itself and the element 80b. This may be accomplished by forming the shield 58b so that it has a larger diameter portion 82 which surrounds the element 80b so that an inductance 68b may be electrically connected between the dielectric element 80b and the shield portion 82.

As described previously, the inductance or finger which forms part of the resonator may be a part of the outer shield which projects into the interruption. Such a finger may be provided as shown in FIG. 13 which illustrates an outer shield 84 in a flat condition prior to being rolled into its usually round shape. This shield 84 represents any one of the shields 58, 58a or 58b.

To provide a finger which forms part of a resonator, a U-shaped opening 86 may be stamped out of the shield to leave a finger 88. The shield may then be rolled in the direction indicated to complete its construction, and the finger 88 may be pressed inwardly into the interruption which is formed during the isolator's construction. This inwardly projecting finger may then be soldered to the dielectric element which forms part of a resonator.

In the case where the shield is to have a larger diameter portion as shown at 82 in FIG. 12, the shield 84 may be rolled over a die which is shaped to expand the diameter of the shield at the proper location.

In applications where a relatively longer finger is to be formed in a shield, such a finger may be provided as shown in FIG. 14. Here, a shield 84a (prior to being rolled) has an opening 90 which is stamped out in the shape of a backward G. This provides a finger 92 whose electrical length extends between the illustrated points A and B. Larger inductance values may be obtained by stamping out a longer meandering finger.

After the finger 92 has been formed and the shield 84a has been rolled, the end (point A) of the finger 92 is bent inwardly to make contact with an outer conductive coating on an underlying dielectric element.

Another form of isolator according to the invention may include a resonator which employs distributed as opposed to discrete inductance to coact with a dielectric body representing a distributed capacitance to create circumferential resonances and thereby provide selective attenuation at a set of frequencies. A resonating dielectric element according to this aspect of the invention is shown in FIGS. 15 and 16. This exemplary resonator 94 has an annular dielectric body 96 defining a central hole 98 through which an inner conductor will pass. Disposed around the hole 98 is an inner conductive coating 100. An outer conductive coating 102 is disposed around the outer circumference of the dielectric body 96, with a slot or gap 104 left in this coating. The outer coating 102 is intended to make electrical contact with an outer shield at a small point on the coating, such as the point 106.

By virtue of the illustrated construction, the resonator 94 is excited into modes of resonance which provide very low impedance mainly at wavelengths .lambda.1 and .lambda.2 given by .lambda.1/4=L and 3/4.lambda.2=L, where L is approximately the mean circumference 108 of the resonator and .lambda. is the wavelength within the dielectric. By proper choice of the length L and the dielectric constant of the dielectric body 96, high RFI attenuation may be achieved in the low VHF band (by virtue of the (.lambda./4) resonance) and at higher frequencies (by virtue of the 3/4.lambda.resonance).

Referring to FIG. 17 in which higher order resonance modes are omitted, a plot is shown of the idealized impedance versus frequency characteristics of the resonator depicted in FIGS. 15 and 16. This illustrates that a low impedance may be created in the vicinity of 60 and 180 megahertz to provide high RFI attenuation at those frequencies.

The reason why this type of resonator provides the characteristics shown in FIG. 17 is as follows. The outer conductive coating 102 essentially forms a distributed inductance, and the inner coating 100, along with the dielectric body 96 and the interrupted outer coating, form a distributed capacitance; the distribution of the inductance and capacitance is in the circumferential direction.

As a result of these distributed parameters, a low reactance is created between the point 106 and the point radially opposite it on the inner coating 100 at frequencies corresponding to odd multiples of (.lambda./4). Thus, substantial RFI attenuation occurs at these frequencies.

One manner in which this type of resonator may be built into an isolator is shown in FIG. 18. As with the previous embodiments, an inner conductor 54c and a relatively small diameter shield 56c receive an RF input which may be coupled to a television tuner via the conductor 54c and a larger diameter shield 58c. Disposed in the interruption established between shields 56c and 58c is an annular dielectric element 108, an annular magnetically absorptive element 110 and the resonator 94. To electrically connect the shield 58c to the conductive coating on the resonator 94, the shield may have a greater diameter where it overlies the resonator 94 and a short electrical connection, such as a solder joint 112, may couple the shield 58c to the resonator's coating as at point 106 (FIG. 16). No other electrical contact occurs between the shield 58c and the resonator 94. With this arrangement, good RFI attenuation is provided over low VHF frequencies as well as higher frequencies.

In certain applications, it may be desirable to include more than one of the FIG. 16 type resonators in a single isolator, along with additional dielectric and magnetically absorptive elements. One such resonator may be selected to provide high RFI attenuation at given frequencies, and another resonator may be selected to provide high RFI attenuation at other frequencies. Such an arrangement is shown in FIG. 19.

In this embodiment, resonators 114 and 116, of the type shown in FIG. 16, sandwich a magnetically absorptive element 118. These resonators may have resonances which occur at different frequencies. The resonant frequencies may be controlled for a given dielectric constant by varying the width of the plating gap 104 (FIG. 16).

Also included in the illustrated interruption are an additional magnetically absorptive element 120 and another dielectric element 122. As shown, solder joints 124 and 126 electrically connect the outer shield 58d to the conductive coatings (not shown in FIG. 19) on resonators 114 and 116, respectively. Further contact between the resonators' conductive coatings is avoided by the shield 58d having an enlarged diameter where it overlies resonators 114 and 116.

As previously stated, the outer shield (such as shield 58c) need not be a conventional braided shield of the type used in coaxial cables. Likewise, the inner shield (56c, for example) need not be a braided shield. Both shields may be part of a connector or equivalent structure which defines an interruption to hold the various dielectric and magnetically absorptive elements.

Although the invention has been described in terms of its applicability to attenuation of RFI in television applications, it will be understood that the invention is not limited to that field. Moreover, those skilled in the art will appreciate that various modifications and alterations may be made to the method and structure described herein without departing from the invention. By way of example only, the conductors in FIGS. 9, 10, 12, 18 and 19 which are shown as receiving an RF input may alternately be coupled to a tuner or the like, with the designated tuner connection being used to receive the RF input. Many other changes will be apparent to those skilled in the art. Accordingly, it is intended that all such modifications and alterations be considered as within the spirit and scope of the invention as defined by the appended claims.