Current Unit for Arc Welding

The present invention relates to an arc welding current supply unit which is arranged to be fed with alternating current and to provide direct current for welding electrodes.

An object of the invention is to provide a novel and useful welding current supply unit which will facilitate welding operations so that an acceptable weld can be made by relatively unskilled persons and which will also enable more satisfactory welding operations to be carried out than was hitherto possible, with the use of conventional welding current units operating at main frequencies.

To this end it is suggested in accordance with the invention that an arc welding current supply unit of the aforementioned type includes a controlled frequency converter operating with a half-period which is less than the average duration of the current and voltage transients caused by short circuits through droplets of the weld material, e.g. less than 3 milliseconds and preferably less than 1.5 milliseconds, and adapted to be connected to the welding electrodes through a transformer in series with a rectifier, and also includes a control device which is adapted to control the converter in a manner such that the arc power remains substantially unchanged irrespective of changes in load caused by the welding operation, wherein said converter is of the series-capacitor type converter, i.e. the primary winding of the transformer is supplied from a d.c. voltage intermediate stage by controlled alternating discharge of one or more capacitors connected in series with said primary winding, and wherein the voltage of the a.c. supply applied to the unit is substantially constant, the control device may be adapted to control the converter in a manner such that it operates at a constant frequency which can be adjusted to a desired value. On the other hand, the control device is arranged to control the operating frequency of the converter so that it is substantially inversely proportional to the square of the voltage of the a.c. supply or the voltage applied to the capacitor or capacitors.

With such a welding current supply unit there is obtained a particularly stable and quiescent arc, irrespective of small variations in the distance between electrode and work piece. In addition, in the event of a short circuit caused by droplets of welding material, the arc will be smoothly re-ignited with small dynamic effect on the molten material.

So that the invention will be more readily understood and optional features thereof made apparent, an embodiment thereof will now be described with reference to the accompanying schematic drawings, in which:

FIG. 1 is a circuit diagram of an a.c. operated arc welding current supply unit having a frequency converter of a type which can be used to advantage in conjunction with the present invention;

FIG. 2 is a circuit diagram of a control circuit intended for use with the current supply unit of FIG. 1;

FIG. 3 illustrates curves denoting voltages and currents which occur during the normal operation of the current supply unit.

The current supply unit shown in FIG. 1 is connected at 10 to a 3-phase a.c. network. The input current is rectified in a six-element full-wave rectifier 11, the rectified output voltage on lines 12, 13 being smoothed by a buffer capacitor 14 and applied to a frequency converter having--as a consequence of the shown arrangement of elements 11 to 14--a low input impedance.

With the illustrated embodiment the switching elements of the frequency converter comprise thyristors 15, 16 which are controlled so as to be alternately energized. The frequency converter is associated with a transformer generally shown at 17 and the primary winding 18 of which is connected in series with load capacitors 19, 20 forming parts of the frequency converter. The secondary winding 21 of the transformer 17 is connected via a bridge rectifier 22 and a choke 29 to welding electrode terminals 24, 25, which terminals are capable of being connected to a winding electrode holder and a work piece to be welded. With the illustrated embodiment there is connected between the terminals 24, 25 a capacitor 26 which is used to maintain a desired open-circuit voltage. A shunt 27 may also be arranged for measuring the load current.

In the case of a fluctuating supply voltage and a constant converter frequency, the desired converter provides a power output which varies substantially proportionally to the square of the supply voltage U.sub.10 between the terminals 10. If the power output from the current unit is to remain substantially constant irrespective of fluctuations in the supply voltage, the frequency of the converter must be varied in proportion to 1/U.sub.10.sup.2.

In FIG. 2, there is shown a control device which is adapted to control the frequency converter in a manner such that the arc power remains substantially constant irrespective of changes in load caused by the welding operation and by changes in input voltage. This control device includes a potentiometer 33 and an oscillator 34, said potentiometer being adapted to control the operating frequency of the oscillator 34. The potentiometer 33 is connected between earth and a negative voltage source which varies substantially inversely proportional to the square of the voltage applied to the frequency converter.

In the shown embodiment, the control device further includes a fixed negative potential 335 and a load resistor 331 connected in series with the potentiometer 33. The supply voltage U.sub.10 is applied to the primary of a transformer 334 the secondary of which is connected through a bridge rectifier 333 to a smoothing capacitor 332 and said load resistor 331. The values of the components are chosen so that the voltage across the resistor 331 is approximately twice that of the voltage across the power adjusting device 33. The voltage across the resistor 331 will therefore vary in proportion to U.sub.10 which in turn means that the voltage across the power adjusting device 33 will vary approximately in proportion to 1/U.sub.10.sup.2 as long as the variations of the supply voltage are small, e.g. not more than .+-.5%. The frequency of the oscillator 34 controlled by the voltage adjusting device 33 will thus also vary in proportion to 1/U.sub.10.sup.2. Instead of using U.sub.10 as the control voltage signal, it is of course possible to use the voltage applied to the converter capacitor 19, 20.

The oscillator 34 includes an integrating circuit comprising an amplifier 340, resistors 341 and 342, and a capacitor 343. The oscillator also includes a level discriminator 344 with associated comparison resistors 345, 346, the resistor 345 being connected to the output of the integrating circuit and the resistor 346 being connected to a voltage source having a fixed negative voltage. The amplifier 340 is controlled in the positive sense by control signals from the potentiometer 33 and in the negative sense by signals from the Q-output of a monostable flip-flop 50 hereinafter described. A voltage adjuster 35 in the form of a potentiometer is provided for adjusting the desired maximum output voltage from the current supply unit, which voltage adjuster 35 is connected via comparison resistors 36 to the terminal 25 of the current supply unit and to an amplifier 37 which serves as a level discriminator.

Control of the state of the thyristors 15, 16 is effected by means of a sensing circuit comprising a transformer 38, the primary side of which is connected via diodes 39, 40 to the anodes A.sub.1, A.sub.2 and cathodes K.sub.1, K.sub.2 of the thyristors 15, 16. One end of the secondary winding of the transformer 38 is earthed and the other end is connected to a comparison circuit which comprises two resistors 41, 42, the resistor 42 having one end thereof connected to a constant negative voltage. The junction between the resistors 41, 42 is further connected to an amplifier 43 which serves as a level discriminator and the change-over point of which is determined by the resistors 41, 42 and the aforementioned constant negative voltage. Each of the amplifiers 344, 37 and 43 is connected to a respective input 45, 46, 47 of an AND gate 48, which operates in a known manner. Thus, in order for the AND gate 48 to emit an output signal, it is necessary for the output signal obtained from the amplifier 344 to be positive. Correspondingly, it is necessary for the output signal from the amplifier 37 to be positive, i.e. for the load voltage on the terminal 25 to be less than the value for which the adjuster 35 is set. Finally, the output signal from the amplifier 43 must be positive, which means that the anode voltage of one of the thyristors 15 or 16 is negative in relation to the cathode, which in turn means that both the thyristors 15 and 16 are de-energized.

The output of the AND gate 48 is connected to the input of the monostable flip-flop 50 which has a pre-determined pulse period corresponding to the recovery time of the thyristors 15, 16, for example 30 .mu.us. Thus, on the output Q of the flip-flop 50 there is obtained a positive voltage pulse for a period of time corresponding to the recovery time of the thyristors 15, 16. This pulse is transmitted through the resistor 342 to the amplifier 340 and is also transmitted to the trigger input T of a JK flip-flop 51, so tht the JK flip-flop 51 changes the status of its outputs at the end of the pulse obtained from the flip-flop 50. The outputs Q, Q of the JK flip-flop 51 are connected to the base electrodes of respective transistors 54, 55 via capacitors 52, 53. The emitters of the transistors 54, 55 are connected to earth while their collectors are connected to the primary windings of respective ignition transformers 56, 57 for the thyristors 15, 16. The other ends of the primary windings are connected to a terminal having a pre-determined positive potential, and the ends of the secondary windings are connected to the cathode K.sub.1 or K.sub.2 and the gate G.sub.1 or G.sub.2 of a respective thyristor 15 or 16. The signals from the outputs of the JK flip-flop 51 will alternatively render the transistors 54, 55 conductive via the capacitors 52, 53, for a short period of time determined by the capacitors 52, 53, so that the thyristors 15, 16 alternately receive a short ignition pulse and thereby alternately supply current to the primary winding 18 of the transformer 17 to produce an alternating current whose frequency is determined by the signals on the inputs 45, 46, 47 of the AND gate 48. With this arrangement a desired substantially constant arc power can be set solely by a corresponding adjustment of the potentiometer 33.

FIG. 3 shows the voltages U.sub.60, U.sub.61 at points 60, 61 and the voltage U.sub.18 across the primary winding 18 of the transformer 17 with normal load on the output of the current supply unit shown in FIGS. 1 and 2. FIG. 3 also shows the output current I.sub.25 through the terminal 25 and the output currents I.sub.15 and I.sub.16 (the latter shown in dash lines) from the thyristors 15, 16. In FIG. 3 the reference t.sub.1 illustrates the point of time when the thyristor 15 is ignited, t.sub.2 the point of time when the thyristor 15 is de-energized and obtains a negative voltage between the anode A.sub.1 and cathode K.sub.1 as a result of the resonant circuit formed by the primary winding 18 of the transformer 17 and the capacitors 19, 20, t.sub.3 the point of time when the thyristor 16 is ignited, and t.sub.4 the point of time when the thyristor 16 is de-energized and obtains a negative anode voltage as a result of said resonant circuit 18, 19, 20. The reference t.sub. 5 shows the point of time at which the thyristor 15 is re-ignited, whereupon the sequence is repeated provided that the load remains substantially unchanged.

The invention is not limited to the frequency converter illustrated and described, but may be used in conjunction with other frequency converters, for example frequency converters having forced commutation or d.c. controlled intermediate stages. If larger fluctuations in supply voltage U.sub.10 than e.g. .+-.5% are likely to occur, there may be added to the varying negative voltage source described with reference to FIG. 2 a multiplying circuit which generates across the resistor 331 a voltage which is truly proportional to 1/U.sub.10.sup.2.