In-Line Coax-to Waveguide Transition Using Dipole

The field of the invention is in the microwave transmission art.

Dielectric rod antennas fed by waveguides are well known in the art. Slot feed radiating systems from coaxial lines are also known. U.S. Pat. No. 3,518,691 to patentee R. H. Hallendorff discloses a dielectric rod antenna excited by a TE.sub.11 mode in a dielectrically loaded circular waveguide. The waveguide is excited by a current loop transition structure from a colinear, end-fire coaxial system. Other patents typical of the prior art are U.S. Pat. Nos. 3,128,467 to patentee D. H. Lanctot, 2,823,381 to patentees J. F. P. Martin et al, 2,611,869 to patentee E. O. Willoughby, and 2,465,245 to patentee F. S. Mabry.

Slot-fed dipoles are discussed in "Microwave Antenna Theory and Design" by Silver (Rad. Lab. Series, Vol. 12, McGraw-Hill Book Co.) at pages 245 through 250. The TE.sub.11 excitation of circular waveguides is discussed at pages 260 through 262 of "Radio Engineers Handbook" 1943 edition by Terman.

A coax-to-wavelength transition is provided which is compact, does not tend to generate higher order modes (which in turn would tend to degrade the radiation characteristics of the antenna system), that is not critical in structural parameters, and in which the interchange of radiators does not appreciably affect the input VSWR.

FIG. 1 is a partial section, schematic representation of the invention coupled to a dielectric rod radiator;

FIG. 2 is an enlarged schematic representation of the dipole and slot termination of the coaxial line; and

FIG. 3 is an enlarged schematic end view of the dipole and coaxial line positioned in a circular waveguide.

Referring to FIG. 1, a conventional coaxial connector 11 (such as a type N) connects with the coaxial line connecting the antenna and feed system to the associated electronic equipment. Connector 11 is mounted on the terminated end 12 of circular waveguide 13. The coax line 14 from the connector 11 may be typical Teflon filled 50-ohm coaxial line. The energy from the coaxial line is transferred to TE.sub.11 mode in the waveguide by a slot-fed dipole having wings 15a and 15b mounted on the outer conductor 16 of the coax. (See FIG. 2). A pair of axial slots 17 and 18 are milled in the coax outer conductor in a plane normal to the dipole axis. The inner conductor 19 of the coax is short-circuited to the outer conductor 16 of the coax by the post 20 which is preferably in the line of the dipole axis. The slot-fed dipole is imbedded in the dielectric 21 filling the waveguide. The waveguide is conventionally coupled to the dielectric rod radiator 22 through the coupling elements 23 (extending into the waveguide) and 24. Stycast is the preferred dielectric material 21 in which to imbed the coax termination. Styrene and alumina may also be used as imbedding dielectrics. The coaxial line 14 feeding the dipole is conventionally loaded 25 with Teflon.

Those practicing this invention will conventionally adapt the physical sizes of the parameters in accord with the desired frequencies of operation. It is desirable that the diameter of the circular waveguide be dimensioned to support substantially only the TE.sub.11 mode. (Typically .lambda..sub.o equal approximately 1.73 d.) It has been found that generally increasing the slot length, increasing the slot width, and loading the slot with dielectric, all lower the resonant frequency. Typical slot length sensitivity is approximately 100 to 125 MHz per 0.1 inch. Typical slot width sensitivity is approximately 32 to 104 MHz per 0.1 inch. In typical embodiments, Teflon loading of the slot(s) lowers the resonant frequency approximately 30 MHz. The length of the dipole is relatively insensitive; about 10 MHz maximum change with normal nominal length changes. Changing the length of the dipole will, as indicated, not shift the resonant frequency very much; it has more effect on the real component of the impedance than the reactive part. Loading the space (26 and 27) between the dipole wings (15a and 15b) and the waveguide wall slightly shifts the resonance, approximately 20 MHz is a typical value. Decreasing the position of the dipole 15a and 15b relative to the back wall 12 also tends to slightly shift the resonant frequency at a rate ranging from substantially zero to approximately 42 MHz per 0.1 inch. The dipole-to-aperture spacing has typically a sensitivity of approximately 12 to 34 MHz per 0.1 inch.